Method and apparatus for transmitting control information in a wireless communication system

ABSTRACT

A wireless communication system is disclosed. Disclosed herein are methods for transmitting a physical uplink control channel (PUCCH) signal in a wireless communication system, which includes setting transmit power for the PUCCH signal, and an apparatus thereof. If the PUCCH signal is transmitted on a subframe configured for a scheduling request (SR), the PUCCH signal includes one or more hybrid automatic repeat request acknowledgement (HARQ-ACK) bits and an SR bit. When determining the transmit power for the PUCCH, the SR bit is selectively considered depending on whether or not a transport block for an uplink shared channel (UL-SCH) is present in the subframe.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a continuation of U.S. patent application Ser. No.14/269,393, filed on May 5, 2014, currently pending, which is acontinuation of U.S. patent application Ser. No. 13/279,215, filed onOct. 21, 2011, now U.S. Pat. No. 8,755,343, which claims the benefit ofearlier filing date and right of priority to Korean Patent ApplicationNo. 2011-0103023, filed on Oct. 10, 2011 and U.S. Provisional PatentApplication No. 61/444,770, filed on Feb. 20, 2011, 61/409,118, filed onNov. 2, 2010, and 61/405,624, filed on Oct. 21, 2010, the contents ofwhich are hereby incorporated by reference herein in their entirety.

DESCRIPTION

[Technical Field]

The present invention relates to a wireless communication system, andmore particularly, to a method and apparatus for transmitting controlinformation in a wireless communication system supporting carrieraggregation (CA).

[Background Art]

Wireless communication systems have been diversified in order to providevarious types of communication services such as voice or data service.In general, a wireless communication system is a multiple access systemcapable of sharing available system resources (bandwidth, transmit poweror the like) so as to support communication with multiple users.Examples of the multiple access system include a Code Division MultipleAccess (CDMA) system, a Frequency Division Multiple Access (FDMA)system, a Time Division Multiple Access (TDMA) system, an OrthogonalFrequency Division Multiple Access (OFDMA) system, a Single CarrierFrequency Division Multiple Access (SC-FDMA) system, and the like.

DISCLOSURE Technical Problem

An object of the present invention is to provide a method and apparatusfor efficiently transmitting control information in a wirelesscommunication system. Another object of the present invention is toprovide a channel format and a signal processing method and apparatusfor efficiently transmitting control information. Another object of thepresent invention is to provide a method and apparatus for efficientlyallocating resources used to transmit control information.

The technical problems solved by the present invention are not limitedto the above technical problems and those skilled in the art canunderstand other technical problems from the following description.

TECHNICAL SOLUTION

To achieve these objects and other advantages and in accordance with thepurpose of the invention, as embodied and broadly described herein, amethod for transmitting a physical uplink control channel (PUCCH) signalby a communication apparatus in a wireless communication system includessetting transmit power for the PUCCH signal. If the PUCCH signal istransmitted on a subframe configured for a scheduling request (SR), thePUCCH signal includes one or more hybrid automatic repeat requestacknowledgement (HARQ-ACK) bits and an SR bit, and the transmit powerfor the PUCCH is determined by using the following equation:

${h( \cdot )} = \frac{n_{HARQ} + n_{SR} - 1}{N}$

where, n_(HARQ) is associated with the number of information bits ofHARQ-ACK, N denotes a positive integer, and n_(SR) is 1 when a transportblock for an uplink shared channel (UL-SCH) is not present at thesubframe and is 0 when the transport block for the UL-SCH is present atthe subframe.

In another aspect of the present invention, a communication apparatusconfigured to transmit a physical uplink control channel (PUCCH) signalin a wireless communication system includes a radio frequency (RF) unit,and a processor configured to set transmit power for the PUCCH signal.If the PUCCH signal is transmitted on a subframe configured for ascheduling request (SR), the PUCCH signal includes one or more hybridautomatic repeat request acknowledgement (HARQ-ACK) bits and an SR bit,and the transmit power for the PUCCH is determined by using thefollowing equation:

${h( \cdot )} = \frac{n_{HARQ} + n_{SR} - 1}{N}$

where, n_(HARQ) is associated with the number of information bits ofHARQ-ACK, N denotes a positive integer, and n_(SR) is 1 when a transportblock for an uplink shared channel (UL-SCH) is not present at thesubframe and is 0 when the transport block for the UL-SCH is present atthe subframe.

The transmit power for the PUCCH signal at a subframe i may bedetermined by using the following equation:

${P_{PUCCH}(i)} = {\min \begin{Bmatrix}{{{P_{{CMAX},c}(i)},}\mspace{509mu}} \\{P_{0_{—}{PUCCH}} + {PL}_{c} + {h( \cdot )} + {\Delta_{F_{—}{PUCCH}}(F)} + {\Delta_{TxD}\left( F^{\prime} \right)} + {g(i)}}\end{Bmatrix}}$

where, P_(PUCCH) (i) denotes transmit power for the PUCCH, P_(CMAX,c)(i)denotes maximum transmit power configured for a serving cell c, P₀ _(_)_(PUCCH) denotes a parameter configured by a higher layer, PL_(c)denotes a downlink path loss estimation value of the serving cell c,Δ_(F) _(_) _(PUCCH) (F) denotes a value corresponding to a PUCCH format,Δ_(T×D)(F′) denotes a value configured by the higher layer or 0, andg(i) denotes a current PUCCH power control adjustment state.

If a transport block for an uplink shared channel (UL-SCH) is notpresent in the subframe, the SR bit indicates actual SR information and,if a transport block for an uplink shared channel (UL-SCH) is present inthe subframe, the SR bit indicates dummy information. The dummyinformation may have a predetermined value. For example, if the SR bitindicates dummy information, the SR bit may be set to a predeterminedvalue of 0 or 1 and may be preferably set to 0.

The SR bit may be attached to the end of the one or more HARQ-ACK bits.

The SR bit may be set to 1 in case of a positive SR and may be set to 0in case of a negative SR.

The one or more HARQ-ACK bits and the SR bit may be joint-coded.

The communication apparatus may be configured with a simultaneousPUCCH-and-physical uplink shared channel (PUSCH) transmission mode.

N may be 2 or 3.

The one or more HARQ-ACK bits and the SR bit may be joint-coded.

The PUCCH signal may be a PUCCH format 3 signal.

Advantageous Effects

According to the present invention, it is possible to efficientlytransmit control information in a wireless communication system. Inaddition, it is possible to provide a channel format and a signalprocessing method for efficiently transmitting control information. Inaddition, it is possible to efficiently allocate resources used totransmit control information.

The effects of the present invention are not limited to theabove-described effects and those skilled in the art can understandother effects from the following description.

DESCRIPTION OF DRAWINGS

The accompanying drawings which are included as a portion of thedetailed description in order to help understanding of the presentinvention provide embodiments of the present invention and describestechnical mapping of the present invention along with the detaileddescription.

FIG. 1 is a view showing physical channels used for a 3^(rd) GenerationPartnership Project (3GPP) Long Term Evolution (LTE) system, which is anexample of a wireless communication system, and a general signaltransmission method using the same.

FIG. 2 is a diagram showing a structure of a radio frame.

FIG. 3A is a diagram showing an uplink signal processing procedure.

FIG. 3B is a diagram showing a downlink signal processing procedure.

FIG. 4 is a diagram showing a Single Carrier Frequency Division MultipleAccess (SC-FDMA) scheme and an Orthogonal Frequency Division MultipleAccess (OFDMA) scheme.

FIG. 5 is a diagram showing a signal mapping scheme on a frequencydomain satisfying a single carrier property.

FIG. 6 is a diagram showing a signal processing procedure of mapping DFTprocess output samples to a single carrier in a clustered SC-FDMA.

FIGS. 7 and 8 are diagrams showing a signal processing procedure ofmapping DFT process output samples to multiple carriers in a clusteredSC-FDMA scheme.

FIG. 9 is a diagram showing a signal processing procedure in a segmentedSC-FDMA scheme.

FIG. 10 is a diagram showing the structure of an uplink subframe.

FIG. 11 is a diagram showing a signal processing procedure oftransmitting a reference signal (RS) in the uplink.

FIGS. 12A and 12B are diagrams showing a demodulation reference signal(DMRS) for a physical uplink shared channel (PUSCH).

FIGS. 13 to 14 are diagrams showing slot level structures of physicaluplink control channel (PUCCH) formats 1a and 1b.

FIGS. 15 and 16 are diagrams showing slot level structures of PUCCHformats 2/2a/2b.

FIG. 17 is a diagram showing ACK/NACK channelization of PUCCH formats 1aand 1b.

FIG. 18 is a diagram showing channelization of a structure in whichPUCCH formats 1/1a/1b and formats 2/2a/2b are mixed within the same PRB.

FIG. 19 is a diagram showing allocation of a PRB used to transmit aPUCCH.

FIG. 20 is a conceptual diagram of management of a downlink componentcarrier in a base station (BS).

FIG. 21 is a conceptual diagram of management of an uplink componentcarrier in a user equipment (UE).

FIG. 22 is a conceptual diagram of the case where one MAC layer managesmultiple carriers in a BS.

FIG. 23 is a conceptual diagram of the case where one MAC layer managesmultiple carriers in a UE.

FIG. 24 is a conceptual diagram of the case where one MAC layer managesmultiple carriers in a BS.

FIG. 25 is a conceptual diagram of the case where a plurality of MAClayers manages multiple carriers in a UE.

FIG. 26 is a conceptual diagram of the case where a plurality of MAClayers manages multiple carriers in a BS.

FIG. 27 is a conceptual diagram of the case where one or more MAC layersmanages multiple carriers in view of reception of a UE.

FIG. 28 is a diagram showing asymmetric carrier aggregation (CA) inwhich a plurality of downlink (DL) component carriers (CCs) and anuplink (UL) CC are linked.

FIGS. 29A to 29F are diagrams showing a structure of PUCCH format 3 anda signal processing procedure therefor.

FIG. 30 is a flowchart illustrating a UL transmission process accordingto the existing 3GPP Rel-8/9;

FIG. 31 is a diagram showing a process of transmitting controlinformation through a PUCCH according to an embodiment of the presentinvention; and

FIG. 32 is a diagram showing a BS and a UE applicable to the presentinvention.

MODE FOR INVENTION

The following technologies may be utilized in various wireless accesssystems such as a Code Division Multiple Access (CDMA) system, aFrequency Division Multiple Access (FDMA) system, a Time DivisionMultiple Access (TDMA) system, an Orthogonal Frequency Division MultipleAccess (OFDMA) system, or a Single Carrier Frequency Division MultipleAccess (SC-FDMA) system. The CDMA system may be implemented as radiotechnology such as Universal Terrestrial Radio Access (UTRA) orCDMA2000. The TDMA system may be implemented as radio technology such asGlobal System for Mobile communications (GSM)/General Packet RadioService (GPRS)/Enhanced Data Rates for GSM Evolution (EDGE). The OFDMAsystem may be implemented as radio technology such as IEEE 802.11(Wi-Fi), IEEE 802.16 (WiMAX), IEEE 802-20 or E-UTRA (Evolved UTRA). TheUTRA system is part of the Universal Mobile Telecommunications System(UMTS). A 3^(rd) Generation Partnership Project Long Term Evolution(3GPP LTE) communication system is part of the E-UMTS (Evolved UMTS),which employs an OFDMA system in downlink and employs an SC-FDMA systemin uplink. LTE-A (Advanced) is an evolved version of 3GPP LTE. In orderto clarify the description, the 3GPP LTE/LTE-A will be focused upon, butthe technical scope of the present invention is not limited thereto.

In a wireless communication system, a user equipment (UE) receivesinformation from a base station (BS) in the downlink (DL) and transmitsinformation to the BS in the uplink (UL). Information transmitted andreceived between the BS and the UE includes data and a variety ofcontrol information, and various physical channels are present accordingto the kind/usage of the transmitted and received information.

FIG. 1 is a view showing physical channels used for a 3^(rd) GenerationPartnership Project (3GPP) Long Term Evolution (LTE) system, which is anexample of a mobile communication system, and a general signaltransmission method using the same.

When a UE is powered on or when the UE newly enters a cell, the UEperforms an initial cell search operation such as synchronization with aBS in step S101. For the initial cell search operation, the UE mayreceive a Primary Synchronization Channel (P-SCH) and a SecondarySynchronization Channel (S-SCH) from the BS so as to performsynchronization with the BS, and acquire information such as a cell ID.Thereafter, the UE may receive a physical broadcast channel from the BSand acquire broadcast information in the cell. Meanwhile, the UE mayreceive a Downlink Reference signal (DL RS) in the initial cell searchstep and confirm a downlink channel state.

The UE which completes the initial cell search may receive a PhysicalDownlink Control Channel (PDCCH) and a Physical Downlink Shared Channel(PDSCH) corresponding to the PDCCH, and acquire more detailed systeminformation in step S102.

Thereafter, the UE may perform a random access procedure in steps S103to S106, in order to complete the access to the eNB. For the randomaccess procedure, the UE may transmit a preamble via a Physical RandomAccess Channel (PRACH) (S103), and may receive a message in response tothe preamble via the PDCCH and the PDSCH corresponding thereto (S104).In contention-based random access, a contention resolution procedureincluding the transmission of an additional PRACH (S105) and thereception of the PDCCH and the PDSCH corresponding thereto (S106) may beperformed.

The UE which performs the above-described procedure may then receive thePDCCH/PDSCH (S107) and transmit a Physical Uplink Shared Channel(PUSCH)/Physical Uplink Control Channel (PUCCH) (S108), as a generaluplink/downlink signal transmission procedure. Control informationtransmitted from the UE to the BS is collectively referred to as uplinkcontrol information (UCI). The UCI includes hybrid automatic repeat andrequest acknowledgement/negative-acknowledgement (HARQ ACK/NACK),scheduling request (SR), channel quality indication (CQI), precodingmatrix indication (PMI), rank indication (RI), etc. The UCI is generallytransmitted via a PUCCH. However, in the case where control informationand traffic data are simultaneously transmitted, the UCI may betransmitted via a PUSCH. The UCI may be aperiodically transmitted via aPUSCH according to a network request/instruction.

FIG. 2 exemplarily shows a radio frame structure. In a cellularOrthogonal Frequency Division Multiplexing (OFDM) radio packetcommunication system, uplink/downlink data packet transmission isperformed in subframe units. One subframe is defined as a predeterminedtime interval including a plurality of OFDM symbols. The 3GPP LTEstandard supports a type 1 radio frame structure applicable to FrequencyDivision Duplex (FDD) and a type 2 radio frame structure applicable toTime Division Duplex (TDD).

FIG. 2(a) is a diagram showing the structure of the type 1 radio frame.A downlink radio frame includes 10 subframes, and one subframe includestwo slots in a time region. A time required for transmitting onesubframe is defined in a Transmission Time Interval (TTI). For example,one subframe may have a length of 1 ms and one slot may have a length of0.5 ms. One slot may include a plurality of OFDM symbols in a timeregion and include a plurality of Resource Blocks (RBs) in a frequencyregion. Since the 3GPP LTE system uses OFDMA in downlink, the OFDMsymbol indicates one symbol duration. The OFDM symbol may be called anSC-FDMA symbol or a symbol duration. RB is a resource allocation unitand includes a plurality of contiguous carriers in one slot.

The number of OFDM symbols included in one slot may be changed accordingto the configuration of a Cyclic Prefix (CP). The CP includes anextended CP and a normal CP. For example, if the OFDM symbols areconfigured by the normal CP, the number of OFDM symbols included in oneslot may be seven. If the OFDM symbols are configured by the extendedCP, the length of one OFDM symbol is increased, the number of OFDMsymbols included in one slot is less than that of the case of the normalCP. In case of the extended CP, for example, the number of OFDM symbolsincluded in one slot may be six. If the channel state is unstable, forexample, if a User Equipment (UE) moves at a high speed, the extended CPmay be used in order to further reduce interference between symbols.

In case of using the normal CP, since one slot includes seven OFDMsymbols, one subframe includes 14 OFDM symbols. At this time, the firsttwo or three OFDM symbols of each subframe may be allocated to aPhysical Downlink Control Channel (PDCCH) and the remaining OFDM symbolsmay be allocated to a Physical Downlink Shared Channel (PDSCH).

The structure of a type 2 radio frame is shown in FIG. 2(b). The type 2radio frame includes two half-frames, each of which is made up of fivesubframes, a downlink pilot time slot (DwPTS), a guard period (GP), andan uplink pilot time slot (UpPTS), in which one subframe consists of twoslots. DwPTS is used to perform initial cell search, synchronization, orchannel estimation. UpPTS is used to perform channel estimation of abase station and uplink transmission synchronization of a user equipment(UE). The guard interval (GP) is located between an uplink and adownlink so as to remove interference generated in the uplink due tomulti-path delay of a downlink signal.

The structure of the radio frame is only exemplary. Accordingly, thenumber of subframes included in the radio frame, the number of slotsincluded in the subframe or the number of symbols included in the slotmay be changed in various manners.

FIG. 3a is a view explaining a signal processing procedure oftransmitting a UL signal at a UE.

In order to transmit the UL signal, a scrambling module 201 of the UEmay scramble a transmitted signal using a UE-specific scrambling signal.The scrambled signal is input to a modulation mapper 202 so as to bemodulated into complex symbols by a Binary Phase Shift Keying (BPSK),Quadrature Phase Shift Keying (QPSK), 16-Quadrature amplitude modulation(QAM) or 64-QAM scheme according to the kind of the transmitted signaland/or the channel state. Thereafter, the modulated complex symbols areprocessed by a transform precoder 203 and are input to a resourceelement mapper 204. The resource element mapper 204 may map the complexsymbols to time-frequency resource elements. The processed signal may betransmitted to the BS via an SC-FDMA signal generator 205 and anantenna.

FIG. 3b is a diagram explaining a signal processing procedure oftransmitting a downlink (DL) signal at a BS.

In a 3GPP LTE system, the BS may transmit one or more codewords in thedownlink. Accordingly, one or more codewords may be processed toconfigure complex symbols by scrambling modules 301 and modulationmappers 302, similar to the UL transmission of FIG. 3a . Thereafter, thecomplex symbols are mapped to a plurality of layers by a layer mapper303, and each layer may be multiplied by a precoding matrix by aprecoding module 304 and may be allocated to each transmission antenna.The processed signals which will respectively be transmitted viaantennas may be mapped to time-frequency resource elements by resourceelement mappers 305, and may respectively be transmitted via OFDM signalgenerators 306 and antennas.

In a wireless communication system, in a case where a UE transmits asignal in the uplink, a Peak-to-Average Ratio (PAPR) may be moreproblematic than the case where a BS transmits a signal in the downlink.Accordingly, as described above with reference to FIGS. 2 and 3, anOFDMA scheme is used to transmit a downlink signal, while an SC-FDMAscheme is used to transmit an uplink signal.

FIG. 4 is a diagram explaining an SC-FDMA scheme and an OFDMA scheme. Inthe 3GPP system, the OFDMA scheme is used in the downlink and theSC-FDMA is used in the uplink.

Referring to FIG. 4, a UE for UL signal transmission and a BS for DLsignal transmission are identical in that a serial-to-parallel converter401, a subcarrier mapper 403, an M-point Inverse Discrete FourierTransform (IDFT) module 404, parallel-to-serial converter 405 and aCyclic Prefix (CP) adding module 406 are included. The UE fortransmitting a signal using an SC-FDMA scheme further includes anN-point DFT module 402. The N-point DFT module 402 partially offsets anIDFT process influence of the M-point IDFT module 404 such that thetransmitted signal has a single carrier property.

FIG. 5 is a diagram explaining a signal mapping scheme in a frequencydomain satisfying the single carrier property in the frequency domain.FIG. 5(a) shows a localized mapping scheme and FIG. 5(b) shows adistributed mapping scheme.

A clustered SC-FDMA scheme which is a modified form of the SC-FDMAscheme will now be described. In the clustered SC-FDMA scheme, DFTprocess output samples are divided into sub-groups in a subcarriermapping process and are non-contiguously mapped in the frequency domain(or subcarrier domain).

FIG. 6 is a diagram showing a signal processing procedure in which DFTprocess output samples are mapped to a single carrier in a clusteredSC-FDMA scheme. FIGS. 7 and 8 are diagrams showing a signal processingprocedure in which DFT process output samples are mapped to multiplecarriers in a clustered SC-FDMA scheme. FIG. 6 shows an example ofapplying an intra-carrier clustered SC-FDMA scheme and FIGS. 7 and 8show examples of applying an inter-carrier clustered SC-FDMA scheme.FIG. 7 shows the case where a subcarrier spacing between contiguouscomponent carriers is set and a signal is generated by a single IFFTblock in a state in which component carriers are contiguously allocatedin a frequency domain and FIG. 8 shows the case where a signal isgenerated by a plurality of IFFT blocks in a state in which componentcarriers are non-contiguously allocated in a frequency domain.

FIG. 9 is a diagram showing a signal processing procedure in a segmentedSC-FDMA scheme.

In the segmented SC-FDMA scheme, IFFTs corresponding in number to acertain number of DFTs are applied such that the DFTs and the IFFTs arein one-to-one correspondence and DFT spreading of the conventionalSC-FDMA scheme and the frequency subcarrier mapping configuration of theIFFTs are extended. Therefore, the segmented SC-FDMA scheme alsoreferred to as an NxSC-FDMA or NxDFT-s-OFDMA scheme. In the presentinvention, the generic term “segmented SC-FDMA” is used. Referring toFIG. 9, the segmented SC-FDMA scheme is characterized in that modulationsymbols of an entire time domain are grouped into N (N is an integergreater than 1) groups and a DFT process is performed on a group unitbasis, in order to relax a single carrier property.

FIG. 10 is a diagram showing the structure of a UL subframe.

Referring to FIG. 10, the UL subframe includes a plurality of slots(e.g., two). Each slot may include SC-FDMA symbols, the number of whichvaries according to the length of a CP. For example, in the case of anormal CP, a slot may include seven SC-FDMA symbols. A UL subframe isdivided into a data region and a control region. The data regionincludes a PUSCH and is used to transmit a data signal such as voice.The control region includes a PUCCH and is used to transmit controlinformation. The PUCCH includes an RB pair (e.g., m=0, 1, 2, 3) locatedat both ends of the data region on the frequency axis and hops betweenslots. The UL control information (that is, UCI) includes HARQ ACK/NACK,Channel Quality Information (CQI), Precoding Matrix Indicator (PMI) andRank Indication (RI).

FIG. 11 is a diagram illustrating a signal processing procedure fortransmitting a Reference Signal (RS) in the uplink. As shown in FIG. 11,data is transformed into a frequency domain signal by a DFT precoder,subjected to frequency mapping and IFFT, and transmitted. In contrast,an RS does not pass through a DFT precoder. More specifically, an RSsequence is directly generated in a frequency domain (step 11),subjected to a localized-mapping process (step 12), subjected to IFFT(step 13), subjected to a CP attachment process (step 14), andtransmitted.

The RS sequence r_(u,v) ^((α))(n) is defined by cyclic shift α of a basesequence and may be expressed by Equation 1.

r _(u,v) ^((α))(n)=e ^(jan) r _(u,v)(n), 0≦n<M _(sc) ^(RS)   Equation 1

where, M_(sc) ^(RS)=mN_(sc) ^(RB) denotes the length of the RS sequence,N_(sc) ^(RB) denotes the size of a resource block represented insubcarrier units, and m is 1≦m≦N_(RB) ^(max,UL). N_(RB) ^(max,UL)denotes a maximum UL transmission band.

A base sequence r _(u,v)(n) is grouped into several groups. u∈{0,1, . .. ,29} denotes a group number, and v corresponds to a base sequencenumber in a corresponding group. Each group includes one base sequencev=0 with a length of M_(sc) ^(RS)=mN_(sc) ^(RB) (1≦m≦5) and two basesequences v=0,1 with a length of M_(sc) ^(RS)=mN_(sc) ^(RB) (6≦m≦N_(RB)^(max,UL)). The sequence group number u and the number v within acorresponding group may be changed with time. Definition of the basesequence r _(u,v)(0), . . . , r _(u,v)(M_(sc) ^(RS)−1) follows asequence length M_(sc) ^(RS).

The base sequence having a length of 3N_(sc) ^(RB) or more may bedefined as follows.

With respect to M_(sc) ^(RS)≧3N_(sc) ^(RB), the base sequence r ^(u,v)(0), . . . , r _(u,v) (M_(sc) ^(RS)−1) is given by the followingEquation 2.

r ^(u,v)(n)=x _(q)(n mod N _(ZC) ^(RS)), 0≦n<M _(sc) ^(RS)   Equation 2

where, a q-th root Zadoff-Chu sequence may be defined by the followingEquation 3.

$\begin{matrix}{{{x_{q}(m)} = e^{{- j}\frac{\pi \; {{qm}{({m + 1})}}}{N_{ZC}^{RS}}}},{0 \leq m \leq {N_{ZC}^{RS} - 1}}} & {{Equation}\mspace{14mu} 3}\end{matrix}$

where, q satisfies the following equation 4.

q=└q+1/2┘+v·(−1)^(└2q┘)

q=N _(ZC) ^(RS)·(u+1)/31   Equation 4

where, the length N_(ZC) ^(RS) of the Zadoff-Chue sequence is given by alargest prime number and thus N_(ZC) ^(RS)<M_(sc) ^(RS) is satisfied.

A base sequence having a length of less than 3N_(sc) ^(RB) may bedefined as follows. First, with respect to M_(sc) ^(RS)=N_(sc) ^(RB) andM_(sc) ^(RS)=2N_(sc) ^(RB), the base sequence is given as shown inEquation 5.

r _(u,v)(n)=e ^(jφ(n)π/4), 0≦n≦M _(sc) ^(RS)−1   Equation 5

where, values φ(n) for M_(sc) ^(RS)=N_(sc) ^(RB) and M_(sc)^(RS)=2N_(sc) ^(RB) are given by the following Table 1, respectively.

TABLE 1 u φ(0), . . . ,φ(11) 0 −1 1 3 −3 3 3 1 1 3 1 −3 3 1 1 1 3 3 3 −11 −3 −3 1 −3 3 2 1 1 −3 −3 −3 −1 −3 −3 1 −3 1 −1 3 −1 1 1 1 1 −1 −3 −3 1−3 3 −1 4 −1 3 1 −1 1 −1 −3 −1 1 −1 1 3 5 1 −3 3 −1 −1 1 1 −1 −1 3 −3 16 −1 3 −3 −3 −3 3 1 −1 3 3 −3 1 7 −3 −1 −1 −1 1 −3 3 −1 1 −3 3 1 8 1 −33 1 −1 −1 −1 1 1 3 −1 1 9 1 −3 −1 3 3 −1 −3 1 1 1 1 1 10 −1 3 −1 1 1 −3−3 −1 −3 −3 3 −1 11 3 1 −1 −1 3 3 −3 1 3 1 3 3 12 1 −3 1 1 −3 1 1 1 −3−3 −3 1 13 3 3 −3 3 −3 1 1 3 −1 −3 3 3 14 −3 1 −1 −3 −1 3 1 3 3 3 −1 115 3 −1 1 −3 −1 −1 1 1 3 1 −1 −3 16 1 3 1 −1 1 3 3 3 −1 −1 3 −1 17 −3 11 3 −3 3 −3 −3 3 1 3 −1 18 −3 3 1 1 −3 1 −3 −3 −1 −1 1 −3 19 −1 3 1 3 1−1 −1 3 −3 −1 −3 −1 20 −1 −3 1 1 1 1 3 1 −1 1 −3 −1 21 −1 3 −1 1 −3 −3−3 −3 −3 1 −1 −3 22 1 1 −3 −3 −3 −3 −1 3 −3 1 −3 3 23 1 1 −1 −3 −1 −3 1−1 1 3 −1 1 24 1 1 3 1 3 3 −1 1 −1 −3 −3 1 25 1 −3 3 3 1 3 3 1 −3 −1 −13 26 1 3 −3 −3 3 −3 1 −1 −1 3 −1 −3 27 −3 −1 −3 −1 −3 3 1 −1 1 3 −3 −328 −1 3 −3 3 −1 3 3 −3 3 3 −1 −1 29 3 −3 −3 −1 −1 −3 −1 3 −3 3 1 −1

TABLE 2 u φ(0), . . . , φ(23) 0 −1 3 1 −3 3 −1 1 3 −3 3 1 3 −3 3 1 1 −11 3 −3 3 −3 −1 −3 1 −3 3 −3 −3 −3 1 −3 −3 3 −1 1 1 1 3 1 −1 3 −3 −3 1 31 1 −3 2 3 −1 3 3 1 1 −3 3 3 3 3 1 −1 3 −1 1 1 −1 −3 −1 −1 1 3 3 3 −1 −31 1 3 −3 1 1 −3 −1 −1 1 3 1 3 1 −1 3 1 1 −3 −1 −3 −1 4 −1 −1 −1 −3 −3 −11 1 3 3 −1 3 −1 1 −1 −3 1 −1 −3 −3 1 −3 −1 −1 5 −3 1 1 3 −1 1 3 1 −3 1−3 1 1 −1 −1 3 −1 −3 3 −3 −3 −3 1 1 6 1 1 −1 −1 3 −3 −3 3 −3 1 −1 −1 1−1 1 1 −1 −3 −1 1 −1 3 −1 −3 7 −3 3 3 −1 −1 −3 −1 3 1 3 1 3 1 1 −1 3 1−1 1 3 −3 −1 −1 1 8 −3 1 3 −3 1 −1 −3 3 −3 3 −1 −1 −1 −1 1 −3 −3 −3 1 −3−3 −3 1 −3 9 1 1 −3 3 3 −1 −3 −1 3 −3 3 3 3 −1 1 1 −3 1 −1 1 1 −3 1 1 10−1 1 −3 −3 3 −1 3 −1 −1 −3 −3 −3 −1 −3 −3 1 −1 1 3 3 −1 1 −1 3 11 1 3 3−3 −3 1 3 1 −1 −3 −3 −3 3 3 −3 3 3 −1 −3 3 −1 1 −3 1 12 1 3 3 1 1 1 −1−1 1 −3 3 −1 1 1 −3 3 3 −1 −3 3 −3 −1 −3 −1 13 3 −1 −1 −1 −1 −3 −1 3 3 1−1 1 3 3 3 −1 1 1 −3 1 3 −1 −3 3 14 −3 −3 3 1 3 1 −3 3 1 3 1 1 3 3 −1 −1−3 1 −3 −1 3 1 1 3 15 −1 −1 1 −3 1 3 −3 1 −1 −3 −1 3 1 3 1 −1 −3 −3 −1−1 −3 −3 −3 −1 16 −1 −3 3 −1 −1 −1 −1 1 1 −3 3 1 3 3 1 −1 1 −3 1 −3 1 1−3 −1 17 1 3 −1 3 3 −1 −3 1 −1 −3 3 3 3 −1 1 1 3 −1 −3 −1 3 −1 −1 −1 181 1 1 1 1 −1 3 −1 −3 1 1 3 −3 1 −3 −1 1 1 −3 −3 3 1 1 −3 19 1 3 3 1 −1−3 3 −1 3 3 3 −3 1 −1 1 −1 −3 −1 1 3 −1 3 −3 −3 20 −1 −3 3 −3 −3 −3 −1−1 −3 −1 −3 3 1 3 −3 −1 3 −1 1 −1 3 −3 1 −1 21 −3 −3 1 1 −1 1 −1 1 −1 31 −3 −1 1 −1 1 −1 −1 3 3 −3 −1 1 −3 22 −3 −1 −3 3 1 −1 −3 −1 −3 −3 3 −33 −3 −1 1 3 1 −3 1 3 3 −1 −3 23 −1 −1 −1 −1 3 3 3 1 3 3 −3 1 3 −1 3 −1 33 −3 3 1 −1 3 3 24 1 −1 3 3 −1 −3 3 −3 −1 −1 3 −1 3 −1 −1 1 1 1 1 −1 −1−3 −1 3 25 1 −1 1 −1 3 −1 3 1 1 −1 −1 −3 1 1 −3 1 3 −3 1 1 −3 −3 −1 −126 −3 −1 1 3 1 1 −3 −1 −1 −3 3 −3 3 1 −3 3 −3 1 −1 1 −3 1 1 1 27 −1 −3 33 1 1 3 −1 −3 −1 −1 −1 3 1 −3 −3 −1 3 −3 −1 −3 −1 −3 −1 28 −1 −3 −1 −1 1−3 −1 −1 1 −1 −3 1 1 −3 1 −3 −3 3 1 1 −1 3 −1 −1 29 1 1 −1 −1 −3 −1 3 −13 −1 1 3 1 −1 3 1 3 −3 −3 1 −1 −1 1 3

RS hopping will now be described.

The sequence group number u in a slot n_(s) may be defined as shown inthe following Equation 6 by a group hopping pattern f_(gh)(n_(s)) and asequence shift pattern f_(ss).

u=(f _(gh)(n _(s))+f_(ss))mod30   Equation 6

where, mod denotes a modulo operation.

17 different hopping patterns and 30 different sequence shift patternsare present. Sequence group hopping may be enabled or disabled by aparameter for activating group hopping provided by a higher layer.

A PUCCH and a PUSCH may have the same hopping pattern, but havedifferent sequence shift patterns.

The group hopping pattern f_(gh)(n_(s)) is the same in the PUSCH and thePUCCH and is given by the following Equation 7.

-   -   Equation 7

${f_{gh}\left( n_{s} \right)} = \left\{ \begin{matrix}{0\mspace{265mu}} & {{{if}\mspace{14mu} {group}\mspace{14mu} {hopping}\mspace{14mu} {is}\mspace{14mu} {diabled}}\;} \\{\left( {\Sigma_{i = 0}^{7}{{c\left( {{8n_{s}} + i} \right)} \cdot 2^{i}}} \right){mod}\mspace{14mu} 30} & {{if}\mspace{14mu} {group}\mspace{14mu} {hopping}\mspace{14mu} {is}\mspace{14mu} {enabled}}\end{matrix} \right.$

where, c(i) denotes a pseudo-random sequence and a pseudo-randomsequence generator may be initialized by

$c_{init} = \left\lfloor \frac{N_{ID}^{cell}}{30} \right\rfloor$

at the start of each radio frame.

The PUCCH and the PUSCH are different in definition of the sequenceshift pattern f_(ss).

The sequence shift pattern f_(ss) ^(PUCCH) of the PUCCH is f_(ss)^(PUCCH)=N_(ID) ^(cell) mod 30 and the sequence shift pattern f_(ss)^(PUSCH) of the PUSCH is f_(ss) ^(PUSCH)=(f_(ss) ^(PUCCH)+Δ_(ss))mod 30.Δ_(ss)∈{0,1, . . . ,29} is configured by a higher layer.

Hereinafter, sequence hopping will be described.

Sequence hopping is applied only to a RS having a length of M_(sc)^(RS)≧6N_(sc) ^(RB).

With respect to an RS having a length of M_(sc) ^(RS)<6N_(sc) ^(RB), abase sequence number v within a base sequence group is v=0.

With respect to an RS having a length of M_(sc) ^(RS)≧6N_(sc) ^(RB), abase sequence number v within a base sequence group in a slot n_(s) isgiven by the following Equation 8.

$\begin{matrix}{v = \left\{ \begin{matrix}{c\left( n_{s} \right)} & {{if}\mspace{14mu} {group}\mspace{14mu} {hopping}\mspace{14mu} {is}\mspace{14mu} {disabled}\mspace{14mu} {and}\mspace{14mu} {sequence}\mspace{14mu} {hopping}\mspace{14mu} {is}\mspace{14mu} {enabled}} \\{0\mspace{34mu}} & {{otherwise}\mspace{590mu}}\end{matrix} \right.} & {{Equation}\mspace{14mu} 8}\end{matrix}$

where, c(i) denotes a pseudo-random sequence and a parameter forenabling sequence hopping provided by a higher layer determines whethersequence hopping is enabled. The pseudo-random sequence generator may beinitialized by

$c_{init} = {{\left\lfloor \frac{N_{ID}^{cell}}{30} \right\rfloor \cdot 2^{5}} + \int_{ss}^{PUSCH}}$

at the start of a radio frame.

An RS for a PUSCH is determined as follows.

The RS sequence r^(PUSCH)(.) for the PUCCH is defined byr^(PUSCH)(m·M_(sc) ^(RS)+n)=r_(u,v) ^((α))(n). m and n satisfy

$\begin{matrix}{{m = 0},1} \\{{n = 0},\ldots \mspace{14mu},{M_{sc}^{RS} - 1}}\end{matrix}$

and satisfy M_(sc) ^(RS)=M_(sc) ^(PUSCH).

In one slot, cyclic shift is α=2□^(n) ^(cs) /12 along withn_(cs)=(n_(DMRS) ⁽¹⁾+n_(DMRS) ⁽²⁾+n_(PRS)(n_(s)))mod 12.

n_(DMRS) ⁽¹⁾ is a broadcast value, n_(DMRS) ⁽²⁾ is given by ULscheduling allocation, and n_(PRS)(n_(s)) is a cell-specific cyclicshift value. n_(PRS)(n_(s)) varies according to a slot number n_(s), andis n_(PRS)(n_(s))=Σ_(i=0) ⁷c(8·n_(s)+i)·2^(i).

c(i) is a pseudo-random sequence and c(i) is a cell-specific value. Thepseudo-random sequence generator may be initialized by

$c_{init} = {{\left\lfloor \frac{N_{ID}^{cell}}{30} \right\rfloor \cdot 2^{5}} + \int_{ss}^{PUSCH}}$

at the start of a radio frame.

Table 3 shows a cyclic shift field and n_(DMRS) ⁽²⁾ at a downlinkcontrol information (DCI) format 0.

TABLE 3 Cyclic shift field at DCI format 0 n_(DMRS) ⁽²⁾ 000 0 001 2 0103 011 4 100 6 101 8 110 9 111 10

A physical mapping method for a UL RS at a PUSCH is as follows.

A sequence is multiplied by an amplitude scaling factor β_(PUSCH) and ismapped to the same set of a physical resource block (PRB) used for thecorresponding PUSCH within the sequence started at r^(PUSCH)(0). l=3 fora normal CP and l=2 for an extended CP. When the sequence is mapped to aresource element (k,l) within a subframe, the order of k is firstincreased and the slot number is then increased.

In summary, if a length is greater than and equal to 3N_(sc) ^(RB), a ZCsequence is used along with cyclic extension. If a length is less than3N_(sc) ^(RB), a computer-generated sequence is used. Cyclic shift isdetermined according to cell-specific cyclic shift, UE-specific cyclicshift and hopping pattern.

FIG. 12A is a diagram showing the structure of a demodulation referencesignal (DMRS) for a PUSCH in the case of normal CP and FIG. 12B is adiagram showing the structure of a DMRS for a PUSCH in the case ofextended CP. In FIG. 12A, a DMRS is transmitted via fourth and eleventhSC-FDMA symbols and, in FIG. 12B, a DMRS is transmitted via third andninth SC-FDMA symbols.

FIGS. 13 to 16 show a slot level structure of a PUCCH format. The PUCCHincludes the following formats in order to transmit control information.

(1) Format 1: This is used for on-off keying (OOK) modulation andscheduling request (SR)

(2) Format 1a and Format 1b: They are used for ACK/NACK transmission

1) Format 1a: BPSK ACK/NACK for one codeword

2) Format 1b: QPSK ACK/NACK for two codewords

(3) Format 2: This is used for QPSK modulation and CQI transmission

(4) Format 2a and Format 2b: They are used for CQI and ACK/NACKsimultaneous transmission.

Table 4 shows a modulation scheme and the number of bits per subframeaccording to a PUCCH format. Table 5 shows the number of RSs per slotaccording to a PUCCH format. Table 6 shows SC-FDMA symbol locations ofan RS according to a PUCCH format. In Table 4, the PUCCH formats 2a and2b correspond to the normal CP case.

TABLE 4 PUCCH Number of bits per format Modulation scheme subframe,M_(bit) 1 N/A N/A 1a BPSK 1 1b QPSK 2 2 QPSK 20 2a QPSK + BPSK 21 2bQPSK + BPSK 22

TABLE 5 PUCCH format Normal CP Extended CP 1, 1a, 1b 3 2 2 2 1 2a, 2b 2N/A

TABLE 6 SC-FDMA symbol PUCCH location of RS format Normal CP Extended CP1, 1a, 1b 2, 3, 4 2, 3 2, 2a, 2b 1, 5 3

FIG. 13 shows PUCCH formats 1a and 1b in the normal CP case. FIG. 14shows PUCCH formats 1a and 1b in the extended CP case. In the PUCCHformats 1a and 1b, the same control information is repeated within asubframe in slot units. Each UE transmits an ACK/NACK signal throughdifferent resources including different cyclic shifts (CSs) (frequencydomain codes) of a computer-generated constant amplitude zero autocorrelation (CG-CAZAC) sequence and orthogonal covers (OCs) ororthogonal cover codes (OCCs) (time domain codes). The OC includes, forexample, a Walsh/DFT orthogonal code. If the number of CSs is 6 and thenumber of OCs is 3, a total of 18 UEs may be multiplexed in a PRB in thecase of using a single antenna. Orthogonal sequences w0, w1, w2 and w3may be applied in a certain time domain (after FFT modulation) or acertain frequency domain (before FFT modulation).

For SR and persistent scheduling, ACK/NACK resources including CSs, OCsand PRBs may be provided to a UE through radio resource control (RRC).For dynamic ACK/NACK and non-persistent scheduling, ACK/NACK resourcesmay be implicitly provided to the UE by a lowest CCE index of a PDCCHcorresponding to a PDSCH.

FIG. 15 shows a PUCCH format 2/2a/2b in the normal CP case. FIG. 16shows a PUCCH format 2/2a/2b in the extended CP case. Referring to FIGS.15 and 16, one subframe includes 10 QPSK data symbols in addition to anRS symbol in the normal CP case. Each QPSK symbol is spread in afrequency domain by a CS and is then mapped to a corresponding SC-FDMAsymbol. SC-FDMA symbol level CS hopping may be applied in order torandomize inter-cell interference. RSs may be multiplexed by CDM using aCS. For example, if it is assumed that the number of available CSs is 12or 6, 12 or 6 UEs may be multiplexed in the same PRB. For example, inthe PUCCH formats 1/1a/1b and 2/2a/2b, a plurality of UEs may bemultiplexed by CS+OC+PRB and CS+PRB.

Length-4 and length-3 OCs for PUCCH formats 1/1a/1b are shown in thefollowing Tables 7 and 8.

TABLE 7 Length-4 orthogonal sequences for PUCCH formats 1/1a/1bOrthogonal sequences Sequence index n_(oc)(n_(s)) [w(0) . . . w(N_(SF)^(PUCCH) − 1)] 0 [+1 +1 +1 +1] 1 [+1 −1 +1 −1] 2 [+1 −1 −1 +1]

TABLE 8 Length-3 orthogonal sequences for PUCCH formats 1/1a/1b Sequenceindex Orthogonal sequences n_(oc)(n_(s)) [w(0) . . . w(N_(SF) ^(PUCCH) −1)] 0 [1 1 1] 1 [1 e^(j2π/3) e^(j4π/3)] 2 [1 e^(j4π/3) e^(j2π/3)]

The OCs for the RS in the PUCCH formats 1/1a/1b is shown in Table 9.

TABLE 9 1a and 1b Sequence index n _(oc)(n_(s)) Normal cyclic prefixExtended cyclic prefix 0 [1 1 1] [1 1] 1 [1 e^(j2π/3) e^(j4π/3)] [1 −1]2 [1 e^(j4π/3) e^(j2π/3)] N/A

FIG. 17 is a diagram explaining ACK/NACK channelization for the PUCCHformats 1a and 1b. FIG. 17 shows the case of Δ_(shift) ^(PUCCH)−2.

FIG. 18 is a diagram showing channelization of a structure in whichPUCCH formats 1/1a/1b and formats 2/2a/2b are mixed within the same PRB.

CS hopping and OC remapping may be applied as follows.

(1) Symbol-based cell-specific CS hopping for inter-cell interferencerandomization

(2) Slot level CS/OC remapping

1) for inter-cell interference randomization

2) slot-based access for mapping between ACK/NACK channels and resourcesk

Resource n, for the PUCCH format 1/1a/1b includes the followingcombination.

(1) CS (=DFT OC in a symbol level) (n_(cs))

(2) OC (OC in a slot level) (n_(0c))

(3) frequency RB (n_(rb))

When indexes representing the CS, the OC and the RB are respectivelyn_(cs), n_(0c) and n_(rb), a representative index n_(r) includes n_(cs),n_(0c) and n_(rb). n_(r) satisfies n_(r)=(n_(cs), n_(0c), n_(rb)).

A CQI, a PMI, a RI, and a combination of a CQI and ACK/NACK may betransmitted through the PUCCH formats 2/2a/2b. Reed Muller (RM) channelcoding may be applied.

For example, in an LTE system, channel coding for a UL CQI is describedas follows. A bit sequence α₀,α₁,α₂,α₃, . . . ,α_(A−1) is channel-codedusing a (20, A) RM code. Table 10 shows a base sequence for the (20, A)code. α₀ and α_(A−1) represent a Most Significant Bit (MSB) and a LeastSignificant Bit (LSB), respectively. In the extended CP case, a maximuminformation bit number is 11 except for the case where the CQI and theACK/NACK are simultaneously transmitted. After the bit sequence is codedto 20 bits using the RM code, QPSK modulation may be applied. BeforeQPSK modulation, coded bits may be scrambled.

TABLE 10 I M_(i,0) M_(i,1) M_(i,2) M_(i,3) M_(i,4) M_(i,5) M_(i,6)M_(i,7) M_(i,8) M_(i,9) M_(i,10) M_(i,11) M_(i,12) 0 1 1 0 0 0 0 0 0 0 01 1 0 1 1 1 1 0 0 0 0 0 0 1 1 1 0 2 1 0 0 1 0 0 1 0 1 1 1 1 1 3 1 0 1 10 0 0 0 1 0 1 1 1 4 1 1 1 1 0 0 0 1 0 0 1 1 1 5 1 1 0 0 1 0 1 1 1 0 1 11 6 1 0 1 0 1 0 1 0 1 1 1 1 1 7 1 0 0 1 1 0 0 1 1 0 1 1 1 8 1 1 0 1 1 00 1 0 1 1 1 1 9 1 0 1 1 1 0 1 0 0 1 1 1 1 10 1 0 1 0 0 1 1 1 0 1 1 1 111 1 1 1 0 0 1 1 0 1 0 1 1 1 12 1 0 0 1 0 1 0 1 1 1 1 1 1 13 1 1 0 1 0 10 1 0 1 1 1 1 14 1 0 0 0 1 1 0 1 0 0 1 0 1 15 1 1 0 0 1 1 1 1 0 1 1 0 116 1 1 1 0 1 1 1 0 0 1 0 1 1 17 1 0 0 1 1 1 0 0 1 0 0 1 1 18 1 1 0 1 1 11 1 0 0 0 0 0 19 1 0 0 0 0 1 1 0 0 0 0 0 0

Channel coding bits b₀,b₁,b₂,b₃, . . . ,b_(B−1) may be generated byEquation 9.

$\begin{matrix}{b_{i} = {\sum\limits_{n = 0}^{A - 1}\; {\left( {a_{n} \cdot M_{i,n}} \right){mod}\mspace{14mu} 2}}} & {{Equation}\mspace{14mu} 9}\end{matrix}$

where, i=0, 1, 2, . . . , B−1 is satisfied.

Table 11 shows an uplink control information (UCI) field for widebandreport (single antenna port, transmit diversity or open loop spatialmultiplexing PDSCH) CQI feedback.

TABLE 11 Field bandwidth Wideband CQI 4

Table 12 shows a UCI field for wideband CQI and PMI feedback. The fieldreports closed loop spatial multiplexing PDSCH transmission.

TABLE 12 Bandwidth 2 antenna ports 4 antenna ports Field Rank = 1 Rank =2 Rank = 1 Rank > 1 Wideband CQI 4 4 4 4 Spatial differential CQI 0 3 03 PMI (Precoding 2 1 4 4 Matrix Index)

Table 13 shows a UCI field for RI feedback for wideband report.

TABLE 13 Bit widths 4 antenna ports 2 antenna Maximum of two Maximum offour Field ports layers layers RI (Rank 1 1 2 Indication)

FIG. 19 shows PRB allocation. As shown in FIG. 19, the PRB may be usedfor PUCCH transmission in a slot n_(s).

A multi-carrier system or a carrier aggregation system refers to asystem for aggregating and utilizing a plurality of carriers having abandwidth smaller than a target bandwidth, for wideband support. When aplurality of carriers having a bandwidth smaller than a target bandwidthis aggregated, the bandwidth of the aggregated carriers may be limitedto a bandwidth used in the existing system, for backward compatibilitywith the existing system. For example, the existing LTE system maysupport bandwidths of 1.4, 3, 5, 10, 15 and 20 MHz and an LTE-Advanced(LTE-A) system evolved from the LTE system may support a bandwidthgreater than 20 MHz using only the bandwidths supported by the LTEsystem. Alternatively, regardless of the bandwidths used in the existingsystem, a new bandwidth may be defined so as to support CA.Multi-carrier may be used interchangeable with CA and bandwidthaggregation. CA includes contiguous CA and non-contiguous CA.

FIG. 20 is a conceptual diagram of management of a downlink componentcarrier in a BS, and FIG. 21 is a conceptual diagram of management of anuplink component carrier in a UE. For convenience of description, it isassumed that a higher layer is a MAC layer in FIGS. 20 and 21.

FIG. 22 is a conceptual diagram of the case where one MAC layer managesmultiple carriers in a BS. FIG. 23 is a conceptual diagram of the casewhere one MAC layer manages multiple carriers in a UE.

Referring to FIGS. 22 and 23, one MAC layer manages one or morefrequency carriers so as to perform transmission and reception. Sincefrequency carriers managed by one MAC layer do not need to be contiguousto each other, resource management is flexible. In FIGS. 22 and 23, onephysical (PHY) layer means one component carrier, for convenience. OnePHY layer does not necessarily mean an independent radio frequency (RF)device. In general, one independent RF device means one PHY layer, butthe present invention is not limited thereto. One RF device may includeseveral PHY layers.

FIG. 24 is a conceptual diagram of the case where a plurality of MAClayers manages multiple carriers in a BS. FIG. 25 is a conceptualdiagram of the case where a plurality of MAC layers manages multiplecarriers in a UE, FIG. 26 is another conceptual diagram of the casewhere a plurality of MAC layers manages multiple carriers in a BS, andFIG. 27 is another conceptual diagram of the case where a plurality ofMAC layers manages multiple carriers in a UE.

In addition to the structures shown in FIGS. 22 and 23, several MAClayers may control several carriers as shown in FIGS. 24 to 27.

Each MAC layer may control each carrier in one-to-one correspondence asshown in FIGS. 24 and 25 and each MAC layer may control each carrier inone-to-one correspondence with respect to some carriers and one MAClayer may control one or more carriers with respect to the remainingcarriers as shown in FIGS. 26 and 27.

The system includes a plurality of carriers such as one carrier to Ncarriers and the carriers may be contiguous or non-contiguous,regardless of UL/DL. A TDD system is configured to manage a plurality(N) of carriers in DL and UL transmission. A FDD system is configuredsuch that a plurality of carriers is used in UL and DL. In the case ofthe FDD system, asymmetric CA in which the number of carriers aggregatedin UL and DL and/or the bandwidths of the carriers are different may besupported.

When the numbers of aggregated component carriers in UL and DL areidentical, it is possible to configure all component carriers so as toenable backward compatibility with the existing system. However,component carriers which do not consider compatibility are not excludedfrom the present invention.

Hereinafter, for convenience of description, it is assumed that, when aPDCCH is transmitted through a DL component carrier #0, a PDSCHcorresponding thereto is transmitted through a DL component carrier #0.However, cross-carrier scheduling may be applied and the PDSCH may betransmitted through another DL component carrier. The term “componentcarrier” may be replaced with other equivalent terms (e.g., cell).

FIG. 28 shows a scenario in which uplink control information (UCI) istransmitted in a wireless communication system supporting CA. Forconvenience, in the present example, it is assumed that the UCI isACK/NACK (A/N). The UCI may include control information channel stateinformation (e.g., CQI, PMI, RI, etc.) or scheduling request information(e.g., SR, etc.).

FIG. 28 is a diagram showing asymmetric CA in which five DL CCs and oneUL CC are linked. The shown asymmetric CA is set from the viewpoint ofUCI transmission. That is, a DL CC-UL CC linkage for UCI and a DL CC-ULCC linkage for data are differently set. For convenience, if it isassumed that one DL CC may transmit a maximum of two codewords, thenumber of UL ACK/NACK bits is at least two. In this case, in order totransmit ACK/NACK for data received through five DL CCs through one ULCC, ACK/NACK of at least 10 bits is necessary. In order to support a DTXstate of each DL CC, at least 12 bits (=5̂5=3125=11.61 bits) arenecessary for ACK/NACK transmission. Since ACK/NACK of at most 2 bitsmay be transmitted in the existing PUCCH formats 1a/1b, such a structurecannot transmit extended ACK/NACK information. For convenience, althoughan example in which the amount of UCI information is increased due to CAis described, the amount of UCI information may be increased due to theincrease in the number of antennas, existence of a backhaul subframe ina TDD system and a relay system, etc. Similarly to ACK/NACK, whencontrol information associated with a plurality of DL CCs is transmittedthrough one UL CC, the amount of control information to be transmittedis increased. For example, in the case where a CQI for a plurality of DLCCs must be transmitted through a UL anchor (or primary) CC, CQI payloadmay be increased.

A DL primary CC may be defined to a DL CC linked with a UL primary CC.Linkage includes implicit and explicit linkage. In the LTE, one DL CCand one UL CC are inherently paired. For example, by LTE pairing, a DLCC linked with a UL primary CC may be referred to as a DL primary CC.This may be regarded as implicit linkage. Explicit linkage indicatesthat a network configures linkage in advance and may be signaled by RRC,etc. In explicit linkage, a DL CC paired with a UL primary CC may bereferred to as a primary DL CC. A UL primary (or anchor) CC may be a ULCC in which a PUCCH is transmitted. Alternatively, the UL primary CC maybe a UL CC in which UCI is transmitted through a PUCCH or a PUSCH. A DLprimary CC may be configured through high layer signaling. A DL primaryCC may be a DL CC in which a UE performs initial access. DL CCsexcluding the DL primary CC may be referred to as DL secondary CCs.Similarly, UL CCs excluding a UL primary CC may be referred to as ULsecondary CCs.

The LTE-A uses the concept of a cell in order to manage radio resources.The cell is defined as a combination of downlink resources and uplinkresources and uplink resources are not indispensable components.Accordingly, the cell may be composed of downlink resources alone or acombination of downlink resources and uplink resources. If CA issupported, a linkage between a downlink resource carrier frequency (orDL CC) and an uplink resource carrier frequency (or UL CC) may beindicated by system information. A cell which operates on a primaryfrequency (or a PCC) is referred to as a primary cell (PCell) and a cellwhich operates on a secondary frequency (or an SCC) is referred to as asecondary cell (SCell). A DL CC and a UL CC may be referred to as a DLcell and a UL cell, respectively. In addition, an anchor (or primary) DLCC and an anchor (or primary) UL CC may be referred to as a DL PCell anda UL PCell, respectively. The PCell is used to perform an initialconnection establishment process or a connection re-establishmentprocess by a UE. The PCell may indicate a cell indicated in a handoverprocess. The SCell may be configured after RRC connection establishmentis performed and may be used to provide additional radio resources. ThePCell and the SCell may be collectively called a serving cell.Accordingly, in case of a UE which is in an RRC_CONNECTED state but isnot configured with CA or does not support CA, only one serving cellincluding only a PCell exists. In contrast, in case of a UE which is inan RRC_CONNECTED state and configured with CA, one or more serving cellsexist and each serving cell includes a PCell and all SCells. For CA, anetwork may configure one or more SCells may be configured for a UEsupporting CA after starting an initial security activation process, inaddition to a PCell which is initially configured in a connectionestablishment process.

DL-UL pairing may be defined only in FDD. Since TDD uses the samefrequency, DL-UL pairing may not be defined. DL-UL linkage may bedetermined from UL linkage through UL E-UTRA Absolute Radio FrequencyChannel Number (EARFCN) information of SIB2. For example, DL-UL linkagemay be acquired through SIB2 decoding during initial access and,otherwise, may be acquired through RRC signaling. Accordingly, only SIB2linkage may be present, but other DL-UL pairing may not be explicitlydefined. For example, in the 5DL:1UL structure of FIG. 28, DL CC #0 andUL CC #0 have an SIB2 linkage relationship and the remaining DL CCs mayhave a relationship with other UL CCs which are not configured for theUE.

In order to support a scenario such as FIG. 28, new scheme is necessary.Hereinafter, a PUCCH format for feedback of UCI (e.g., multiple A/Nbits) in a communication system supporting a carrier aggregation isreferred to a CA PUCCH format (or PUCCH format 3). For example, PUCCHformat 3 is used to transmit A/N information (possibly, including DTXstate) corresponding PDSCH (or PDCCH) received on multiple DL servingcells.

FIGS. 29A to 29F show the structure of PUCCH format 3 and a signalprocessing procedure therefore according to the present embodiment.

FIG. 29A shows the case where the PUCCH format according to the presentembodiment is applied to the structure of the PUCCH format 1 (normalCP). Referring to FIG. 29A, a channel coding block channel-codesinformation bits a_0, a_1, . . . , and a_M−1 (e.g., multiple ACK/NACKbits) and generates encoded bits (coded bits or coding bits) (orcodewords) b_0, b_1, . . . , and b_N−1. M denotes the size of theinformation bits and N denotes the size of the encoded bits. Theinformation bits include UCI, for example, multiple ACK/NACK bits for aplurality of data (or PDSCHs) received through a plurality of DL CCs.The information bits a_0, a_1, . . . , and a_M−1 are joint-codedregardless of the kind/number/size of UCI configuring the informationbits. For example, if the information bits include multiple ACK/NACKbits for a plurality of DL CCs, channel coding is performed not withrespect to each DL CC or each ACK/NACK bit, but with respect to entirebit information. Thus, a single codeword is generated. Channel codingincludes but not limited to simplex repetition, simplex coding, ReedMuller (RM) coding, punctured RM coding, tail-biting convolutionalcoding (TBCC), low-density parity-check (LDPC) and turbo-coding.Although not shown, the encoded bits can be rate-matched inconsideration of a modulation order and the amount of resources. Therate-matching function may be included in the channel coding block ormay be performed using a separate functional block. For example, thechannel coding block may perform (32, 0) RM coding with respect to aplurality of control information so as to obtain a single codeword andperform circular buffer rate-matching.

A modulator modulates the encoded bits b_0, b_1, . . . , and b_N−1 andgenerates modulation symbols c_0, c_1, . . . , and c_L−1. L denotes thesize of the modulation symbols. The modulation method is performed bychanging the amplitude and phase of the transmitted signal. Themodulation method includes, for example, n-phase shift keying (PSK) andn-quadrature amplitude modulation (QAM) (n is an integer greater than orequal to 2). More specifically, the modulation method may include binaryPSK (BPSK), quadrature PSK (QPSK), 8-PSK, QAM, 16-QAM, 64-QAM, etc.

A divider divides the modulation symbols c_0, c_1, . . . , and c_L−1into slots. The order/pattern/method of dividing the modulation symbolsto slots is not specially limited. For example, the divider may dividethe modulation symbols to slots sequentially from the head (local type).In this case, as shown, the modulation symbols c_0, c_1, . . . , andc_L/2−1 may be divided to a slot 0 and the modulation symbols c_L/2,c_L/2+1, . . . , and c_L−1 may be divided to a slot 1. The modulationsymbols may be interleaved (or permutated) when being divided to theslots. For example, even-numbered modulation symbols may be divided tothe slot 0 and odd-numbered modulation symbols may be divided to theslot 1. The order of the modulation process and the division process maybe changed. Instead of dividing different coding bits into slots, thesame coding bits may be configured to be repeated in slot units. In thiscase, the divider may be omitted.

A DFT precoder performs DFT precoding (e.g., 12-point DFT) with respectto the modulation symbols divided to the slots, in order to generate asingle carrier waveform. Referring to the drawing, the modulationsymbols c_0, c_1, . . . , and c_L/2−1 divided to the slot 0 areDFT-precoded to DFT symbols d_0, d_1, . . . , and d_L/2−1, and themodulation symbols c_L/2, c_L/2+1, . . . , and c_L−1 divided to the slot1 are DFT-precoded to DFT symbols d_L/2, d_L/2+1, . . . , and d_L−1. DFTprecoding may be replaced with another linear operation (e.g., Walshprecoding). The DFT precoder may be replaced with a CAZAC modulator. TheCAZAC modulator modulates the modulation symbols c_0, c_1, . . . , andc_L/2−1 and c_L/2, c_L/2+1, . . . , and c_L−1 divided to the slots withcorresponding sequences and generate CAZAC modulation symbols d_0, d_1,. . . , d_I/2−1 and d_L/2, d_L/2+1, . . . , and d_L−1. The CAZACmodulator includes, for example, CAZAC sequences or sequences for LTEcomputer generated (CG) 1 RB. For example, if the LTE CG sequences arer_0, . . . , and r_L/2−1, the CAZAC modulation symbols may bed_n=c_n*r_n or d_n=conj(c_n)*r_n.

A spreading block spreads a signal subjected to DFT at an SC-FDMA symbollevel (time domain). Time domain spreading of the SC-FDMA symbol levelis performed using a spreading code (sequence). The spreading codeincludes a quasi-orthogonal code and an orthogonal code. Thequasi-orthogonal code includes, but is not limited to, a pseudo noise(PN) code. The orthogonal code includes, but is not limited to, a Walshcode and a DFT code. Although the orthogonal code is described as arepresentative example of the spreading code for ease of description inthe present specification, the orthogonal code is only exemplary and maybe replaced with a quasi-orthogonal code. A maximum value of a spreadingcode size (or a spreading factor (SF)) is restricted by the number ofSC-FDMA symbols used to transmit control information. For example, inthe case where four SC-FDMA symbols are used to transmit controlinformation in one slot, (quasi-)orthogonal codes w0, w1, w2 and w3having a length of 4 may be used in each slot. The SF means thespreading degree of the control information and may be associated withthe multiplexing order of a UE or the multiplexing order of an antenna.The SF may be changed to 1, 2, 3, 4, . . . according to requirements ofthe system and may be defined between a BS and a UE in advance or may beinformed to the UE through DCI or RRC signaling. For example, in thecase where one of SC-FDMA symbols for control information is puncturedin order to transmit an SRS, a spreading code with a reduced SF (e.g.,SF=3 instead of SF=4) may be applied to the control information of theslot.

The signal generated through the above procedure is mapped tosubcarriers in a PRB, is subjected to IFFT, and is transformed into atime domain signal. The time domain signal is attached with CP and thegenerated SC-FDMA symbols are transmitted through a RF stage.

On the assumption that ACK/NACK for five DL CCs is transmitted, eachprocedure will be described in detail. In the case where each DL CC maytransmit two PDSCHs, the number ACK/NACK bits may be 12 if a DTX stateis included. In consideration of QPSK modulation and SF=4 timespreading, a coding block size (after rate-matching) may be 48 bits. Theencoded bits may be modulated into 24 QPSK symbols and 12 symbols of thegenerated QPSK symbols are divided to each slot. In each slot, 12 QPSKsymbols are converted into 12 DFT symbols by a 12-point DFT operation.In each slot, 12 DFT symbols are spread to four SC-FDMA symbols usingthe spreading code having SF=4 in a time domain and are mapped. Since 12bits are transmitted through [2 bits*12 subcarriers+8 SC-FDMA symbols],the coding rate is 0.0625 (=12/192). In case of SF=4, a maximum of fourUEs may be multiplexed per 1PRB.

The signal processing procedure described with reference to FIG. 29A isonly exemplary and the signal mapped to the PRB in FIG. 29A may beobtained using various equivalent signal processing procedures. Thesignal processing procedures equivalent to FIG. 29A will be describedwith reference to FIGS. 29B to 29F.

FIG. 29B is different from FIG. 29A in the order of the DFT precoder andthe spreading block. In FIG. 29A, since the function of the spreadingblock is equal to multiplication of a DFT symbol sequence output fromthe DFT precoder by a specific constant at an SC-FDMA symbol level, thevalue of the signal mapped to the SC-FDMA symbols is identical even whenthe order of the DFT precoder and the spreading block is changed.Accordingly, the signal processing procedure for the PUCCH format 3 maybe performed in order of channel coding, modulation, division, spreadingand DFT precoding. In this case, the division process and the spreadingprocess may be performed by one functional block. For example, themodulation symbols may be spread at the SC-FDMA symbol level while beingalternately divided to slots. As another example, the modulation symbolsare copied to suit the size of the spreading code when the modulationsymbols are divided to slots, and the modulation symbols and theelements of the spreading code may be multiplied in one-to-onecorrespondence. Accordingly, the modulation symbol sequence generated ineach slot is spread to a plurality of SC-FDMA symbols at the SC-FDMAsymbol level. Thereafter, the complex symbol sequence corresponding toeach SC-FDMA symbol is DFT-precoded in SC-FDMA symbol units.

FIG. 29C is different from FIG. 29A in the order of the modulator andthe divider. Accordingly, the signal processing procedure for the PUCCHformat 3 may be performed in order of joint channel coding and divisionat a subframe level and modulation, DFT precoding and spreading at eachslot level.

FIG. 29D is different from FIG. 29C in order of the DFT precoder and thespreading block. As described above, since the function of the spreadingblock is equal to multiplication of a DFT symbol sequence output fromthe DFT precoder by a specific constant at an SC-FDMA symbol level, thevalue of the signal mapped to the SC-FDMA symbols is identical even whenthe order of the DFT precoder and the spreading block is changed.Accordingly, the signal processing procedure for the PUCCH format 3 maybe performed by joint channel coding and division at a subframe leveland modulation at each slot level. The modulation symbol sequencegenerated in each slot is spread to a plurality of SC-FDMA symbols atthe SC-FDMA symbol level and the modulation symbol sequencecorresponding to each SC-FDMA symbol is DFT-precoded in SC-FDMA symbolunits. In this case, the modulation process and the spreading processmay be performed by one functional block. For example, the generatedmodulation symbols may be directly spread at the SC-FDMA symbol levelwhile the encoded bits are modulated. As another example, the modulationsymbols are copied to suit the size of the spreading code when theencoded bits are modulated, and the modulation symbols and the elementsof the spreading code may be multiplied in one-to-one correspondence.

FIG. 29E shows the case where the PUCCH format 3 according to thepresent embodiment is applied to the structure of the PUCCH format 2(normal CP) and FIG. 29F shows the case where the PUCCH format 3according to the present embodiment is applied to the structure of thePUCCH format 2 (extended CP). The basic signal processing procedure isequal to those described with respect to FIGS. 29A to 29D. As thestructure of the PUCCH format 2 of the existing LTE is reused, thenumber/locations of UCI SC-FDMA symbols and RS SC-FDMA symbols in thePUCCH format 3 is different from that of FIG. 29A.

Table 14 shows the location of the RS SC-FDMA symbol in the PUCCH format3. It is assumed that the number of SC-FDMA symbols in a slot is 7(indexes 0 to 6) in the normal CP case and the number of SC-FDMA symbolsin a slot is 6 (indexes 0 to 5) in the extended CP case.

TABLE 14 SC-FDMA symbol location of RS Normal CP Extended CP Note PUCCHformat 3 2, 3, 4 2, 3 PUCCH format 1 is reused 1, 5 3 PUCCH format 2 isreused

Here, the RS may reuse the structure of the existing LTE. For example,an RS sequence may be defined using cyclic shift of a base sequence (seeEquation 1).

A signal processing procedure of a PUCCH format 3 will be describedusing equations. For convenience, it is assumed that a length-5 OCC isused (e.g., FIGS. 29E to 29F).

First, a bit block b(0), . . . ,b(M_(bit)−1) is scrambled using aUE-specific scrambling sequence. The bit block b(0), . . . ,b(M_(bit)−1) may correspond to coded bits b_0, b_1, . . . , b_N−1 ofFIG. 29A. The bit block b(0), . . . ,b(M_(bit)−1) may include at leastone of an ACK/NACK bit, a CSI bit and an SR bit. The scrambled bit block{tilde over (b)}(0), . . . ,{tilde over (b)}(M_(bit)−1) may be generatedby the following equation.

{tilde over (b)}(i)=(b(i)+c(i))mod 2   Equation 10

where, c(i) denotes a scrambling sequence. c(i) includes a pseudo-randomsequence defined by a length-31 gold sequence and may be generated bythe following equation. mod denotes a modulo operation.

c(n)=(x ₁(n+N _(C))+x ₂(n+N _(C)))mod 2

x ₁(n+31)=(x ₁(n+3)+x ₁(n))mod 2

x ₂(n+31)=(x ₂(n+3)+x ₂(n+2)+x ₂(n+1)+x ₂(n))mod 2   Equation 11

where, N_(C)=1600. A first m-sequence is initialized to x₁(0)=1,x₁(n)=0, n=1,2, . . . ,30. A second m-sequence is initialized toc_(init)=Σ_(i=0) ³⁰x₂(i)·2^(i). c_(init) may be initialized toc_(init)=(└n_(s)/2┘+1)·(2N_(ID) ^(cell)+1)·2¹⁶+n_(RNTI) whenever asubframe is started. n_(s) denotes a slot number in a radio frame,N_(ID) ^(cell) denotes a physical layer cell identity, and n_(RNTI)denotes a radio network temporary identifier.

The scrambled bit block {tilde over (b)}(0), . . . ,{tilde over(b)}(M_(bit)−1) is modulated and a complex modulation symbol block d(0),. . . ,d(M_(symb)−1) is generated. When QPSK modulation is performed,M_(symb)=M_(bit)/2=2N_(sc) ^(RB). The complex modulation symbol blockd(0), . . . ,d(M_(symb)−1) correspond to modulation symbols c_0, c_1, .. . , c_N−1 of FIG. 29A.

The complex modulation symbol block d(0), . . . ,d(M_(symb)−1) areblock-wise spread using an orthogonal sequence w_(n) _(oc) (i). N_(SF,0)^(PUCCH)+N_(SF,1) ^(PUUCH) complex symbol sets are generated by thefollowing equation. A frequency division/spreading process of FIG. 29Bis performed by the following equation. Each complex symbol setcorresponds to one SC-FDMA symbol and has N_(sc) ^(RB) (e.g., 12)complex modulation values.

$\begin{matrix}{{y_{n}^{(\overset{\sim}{p})}(i)} = \left\{ {{{\begin{matrix}{{{w_{n_{oc},0}^{(\overset{\sim}{p})}\left( \overset{\_}{n} \right)} \cdot e^{j\; \pi {\lfloor{{n_{cs}^{cell}{({n_{s},l})}}\text{/}64}\rfloor}\text{/}2} \cdot {d(i)}}\mspace{70mu}} & {n < N_{{SF},0}^{PUCCH}} \\{{w_{n_{oc},1}^{(\overset{\sim}{p})}\left( \overset{\_}{n} \right)} \cdot e^{j\; \pi {\lfloor{{n_{cs}^{cell}{({n_{s},l})}}\text{/}64}\rfloor}\text{/}2} \cdot {d\left( {N_{sc}^{RB} + i} \right)}} & {{otherwise}\mspace{25mu}}\end{matrix}\overset{\_}{n}} = {{n\mspace{14mu} {mod}\mspace{14mu} N_{{SF},0}^{PUCCH}n} = 0}},\ldots,{{N_{{SF},0}^{PUCCH} + N_{{SF},1}^{PUCCH} - {1i}} = 0},1,\ldots,{N_{sc}^{RB} - 1}} \right.} & {{Equation}\mspace{14mu} 12}\end{matrix}$

where, N_(SF,0) ^(PUCCH) and N_(SF) ^(PUCCH) correspond to the number ofSC-FDMA symbols used for PUCCH transmission at a slot 0 and a slot 1,respectively. In case of using a normal PUCCH format 3, N_(SF,0)^(PUCCH)=N_(SF,1) ^(PUCCH)=5. In case of using a shortened PUCCH format3, N_(SF,0) ^(PUCCH)=5 and N_(SF,1) ^(PUCCH)=4. w_(n) _(oc,0)^(({tilde over (p)}))(i) and w_(n) _(oc,1) ^(({tilde over (p)}))(i)respectively indicate orthogonal sequences applied to a slot 0 and aslot 1 and are given by Table 15. n_(oc) ^(({tilde over (p)})) denotesan orthogonal sequence index (or an orthogonal code index). └ ┘ denotesa flooring function. n_(cs) ^(cell)(n_(s),l) may be n_(cs)^(cell)(n_(s),l)=Σ_(i=0) ⁷c(8N_(symb) ^(UL)·n_(s)+8l+i)·2^(i). c(i) maybe given by Equation 11 and may be initialized to c_(init)=N_(ID)^(cell) at the beginning of every radio frame. n=0, . . . , N_(SF,0)^(PUCCH)+N_(SF,1) ^(PUUCH)−1. {tilde over (p)} denotes an indexcorresponding to an antenna port number.

Table 15 shows an orthogonal w_(n) _(oc) (i) according to theconventional method.

TABLE 15 Orthogonal sequence Sequence [w_(n) _(oc) (0) . . . w_(n) _(oc)(N_(SF) ^(PUCCH) − 1)] index n_(oc) N_(SF) ^(PUCCH) = 5 N_(SF) ^(PUCCH)= 4 0 [1 1 1 1 1] [+1 +1 +1 +1] 1 [1 e^(j2π/5) e^(j4π/5) e^(j6π/5)e^(j8π/5)] [+1 −1 +1 −1] 2 [1 e^(j4π/5) e^(j8π/5) e^(j2π/5) e^(j6π/5)][+1 −1 −1 +1] 3 [1 e^(j6π/5) e^(j2π/5) e^(j8π/5) e^(j4π/5)] [+1 +1 −1−1] 4 [1 e^(j8π/5) e^(j6π/5) e^(j4π/5) e^(j2π/5)] —

In Table 15, N_(SF) ^(PUCCH)=5 orthogonal sequence (or code) isgenerated by the following equation.

$\begin{matrix}\left\lbrack {e^{j\frac{2{\pi \cdot 0 \cdot n_{oc}}}{5}}\mspace{14mu} e^{j\frac{2{\pi \cdot 1 \cdot n_{oc}}}{5}}\mspace{14mu} e^{j\frac{2{\pi \cdot 2 \cdot n_{oc}}}{5}}\mspace{14mu} e^{j\frac{2{\pi \cdot 3 \cdot n_{oc}}}{5}}\mspace{14mu} e^{j\frac{2{\pi \cdot 4 \cdot n_{oc}}}{5}}} \right\rbrack & {{Equation}\mspace{14mu} 13}\end{matrix}$

Resources for the PUCCH format 3 are identified by a resource indexn_(PUCCH) ^((3,{tilde over (p)})). For example, n_(0c)^(({tilde over (p)})) may be n_(0c) ^(({tilde over (p)}))=n_(PUCCH)^((3,{tilde over (p)})) mod N_(SF,1) ^(PUUCH). n_(PUCCH)^((3,{tilde over (p)})) may be indicated through a transmit powercontrol (TPC) field of an SCell PDCCH. More specifically, n_(oc)^(({tilde over (p)})) for each slot may be given by the followingequation.

$\begin{matrix}{{n_{{oc},0}^{(\overset{\sim}{p})} = {n_{PUCCH}^{({3,\overset{\sim}{p}})}\mspace{14mu} {mod}\mspace{14mu} N_{{SF},1}^{PUCCH}}}{n_{{oc},1}^{(\overset{\sim}{p})} = \left\{ \begin{matrix}{\left( {3n_{{oc},0}^{(\overset{\sim}{p})}} \right){mod}\mspace{14mu} N_{{SF},1}^{PUCCH}} & {{{if}\mspace{14mu} N_{{SF},1}^{PUCCH}} = 5} \\{{n_{{oc},0}^{(\overset{\sim}{p})}\mspace{14mu} {mod}\mspace{14mu} N_{{SF},1}^{PUCCH}}\mspace{20mu}} & {{otherwise}\mspace{56mu}}\end{matrix} \right.}} & {{Equation}\mspace{14mu} 14}\end{matrix}$

where, n_(oc) ^(({tilde over (p)})) denotes a sequence index valuen_(oc) ^(({tilde over (p)})) for a slot 0 and n_(oc,1)^(({tilde over (p)})) denotes a sequence index value n_(oc)^(({tilde over (p)})) for a slot 1. In case of a normal PUCCH format 3,N_(SF,0) ^(PUCCH)=N_(SF,1) ^(PUCCH)=5. In case of a shortened PUCCHformat 3, N_(SF) ^(PUCCH)=5, N_(SF,1) ^(PUCCH)=4.

According to the above equation, in case of the shortened PUCCH format 3(that is, N_(SF,1) ^(PUCCH)=4), an orthogonal sequence of the same indexn_(0c,1) ^(({tilde over (p)})) is used in the slot 0 and the slot 1.

A block-spread complex symbol set may be cyclic-shifted according to thefollowing equation.

{tilde over (y)} _(n) ^(({tilde over (p)}))(i)=y _(n)^(({tilde over (p)}))((i+n _(cs) ^(cell)(n_(s),l))mod N_(sc) ^(RB))  Equation 15

where, n_(s) denotes a slot number within a radio frame and l denotes anSC-FDMA symbol number within a slot. n_(cs) ^(cell)(n_(s),l) is definedby Equation 12. n=0, . . . , N_(SF,0) ^(PUCCH)+N_(SF,1) ^(PUCCH)−1.

Each cyclic-shifted complex symbol set is transform-precoded accordingto the following equation. As a result, a complex symbol blockz^(({tilde over (p)}))(0), . . . , z^(({tilde over (p)}))((N_(SF,0)^(PUCCH)+N_(SF,1) ^(PUCCH))N_(sc) ^(RB)−1) is generated.

$\begin{matrix}{{{z^{(\overset{\sim}{p})}\left( {{n \cdot N_{sc}^{RB}} + k} \right)} = {\frac{1}{\sqrt{P}}\frac{1}{\sqrt{N_{sc}^{RB}}}{\sum\limits_{i = 0}^{N_{sc}^{RB} - 1}\; {{{\overset{\sim}{y}}_{n}^{(\overset{\sim}{p})}(i)}e^{{- j}\frac{2\pi \; {ik}}{N_{sc}^{RB}}}}}}}{{k = 0},\ldots,{N_{sc}^{RB} - 1}}{{n = 0},\ldots,{N_{{SF},0}^{PUCCH} + N_{{SF},1}^{PUCCH} - 1}}} & {{Equation}\mspace{14mu} 16}\end{matrix}$

The complex symbol block z^(({tilde over (p)}))(0), . . .,z^(({tilde over (p)}))((N_(SF,0) ^(PUCCH)+N_(SF,1) ^(PUCCH))N_(sc)^(RB)−1) is mapped to physical resources after power control. Powercontrol will be described in detail below. A PUCCH uses one resourceblock in each slot of a subframe. In the resource block,z^(({tilde over (p)}))(0), . . . , z^(({tilde over (p)}))((N_(SF,0)^(PUCCH)+N_(SF,1) ^(PUCCH))N_(sc) ^(RB)−1) is mapped to a resourceelement (k,l) on an antenna port p, which is not used for RStransmission (see Table 14). Mapping is performed in ascending order ofk, l then slot number, starting from the first slot of a subframe. kdenotes a subcarrier index and l denotes an SC-FDMA symbol index in aslot. P denotes the number of antenna ports used for PUCCH transmission.p denotes an antenna port number used for PUCCH transmission and arelationship between p and {tilde over (p)} is shown in the followingtable.

TABLE 16 Antenna port number p (function of the number P of antennaports configured for PUCCH) Index {tilde over (p)} 1 2 4 0 100 200 — 1 —201 —

Hereinafter, a conventional PUCCH power control method will bedescribed. The PUCCH format 3 will be focused upon. If a serving cell cis a primary cell, UE transmit power P_(PUCCH)(i) for PUCCH transmissionat a subframe i is given as follows.

$\begin{matrix}{{P_{PUCCH}(i)} = {\min \begin{Bmatrix}{{{P_{{CMAX},c}(i)},}\mspace{506mu}} \\{P_{0_{—}{PUCCH}} + {PL}_{c} + {h( \cdot )} + {\Delta_{F_{—}{PUCCH}}(F)} + {\Delta_{TxD}\left( F^{\prime} \right)} + {g(i)}}\end{Bmatrix}}} & {{Equation}\mspace{14mu} 17}\end{matrix}$

P_(CMAX,c)(i) denotes maximum transmit power of a UE configured for theserving cell c.

P_(O) _(_) _(PUCCH) is a parameter composed of a sum of P_(O) _(_)_(NOMINAL) _(_) _(PUCCH) and P_(O) _(_) _(UE) _(_) _(PUCCH). P_(O) _(_)_(NOMINAL) _(_) _(PUCCH) and P_(O) _(_) _(UE) _(_) _(PUCCH) are providedby a higher layer (e.g., an RRC layer).

PL_(c) denotes a downlink path loss estimation value of the serving cellc.

A parameter Δ_(F) _(_) _(PUCCH)(F) is provided by a higher layer. EachΔ_(F) _(_) _(PUCCH)(F) value denotes a value corresponding to a PUCCHformat relative to a PUCCH format 1a.

In the case where a UE is configured to transmit a PUCCH using twoantenna ports by a higher layer, a parameter Δ_(T×D)(F′) is provided bya higher layer. Otherwise, that is, in the case where a UE is configuredto transmit a PUCCH using a single antenna port, Δ_(T×D)(F′) is 0. Thatis, Δ_(T×D)(F′) corresponds to a power compensation value considering anantenna port transmission mode.

h(.) is dependent on a PUCCH format. h(.) is a function having at leastone of n_(CQI), n_(HARQ) and n_(SR) as a parameter.

In case of the PUCCH format 3,

${h( \cdot )} = \frac{n_{HARQ} + n_{SR} - 1}{2}$

is given.

where, n_(CQI) denotes a power compensation value associated withchannel quality information. More specifically, n_(CQI) corresponds tothe number of information bits for channel quality information. n_(SR)denotes a power compensation value associated with SR. Morespecifically, n_(SR) corresponds to the number of SR bits. If a timewhen HARQ-ACK will be transmitted through the PUCCH format 3 is asubframe (referred to as an SR subframe) configured for SR transmission,a UE transmits an SR bit (e.g., 1 bit) and one or more HARQ-ACK bits,which are joint-coded, through the PUCCH format 3. Accordingly, the sizeof the control information transmitted through the PUCCH format 3 on anSR subframe is always greater than a HARQ-ACK payload size by 1.Accordingly, n_(SR) is 1 if a subframe i is an SR subframe and is 0 if asubframe i is a non-SR subframe.

n_(HARQ) denotes a power compensation value associated with HARQ-ACK.More specifically, n_(HARQ) is associated with the number of (valid oractual) information bits. In addition, n_(HARQ) is defined as the numberof transport blocks received on a downlink subframe. That is, powercontrol is determined by the number of PDCCHs for packets scheduled byan eNB and successfully decoded by an UE. In contrast, a HARQ-ACKpayload size is determined by the number of configured DL cells.Accordingly, if a UE has one serving cell, n_(HARQ) is the number ofHARQ bits transmitted on a subframe i. If a UE has a plurality ofserving cells, n_(HARQ) may be given as follows. In case of TDD, if a UEreceives an SPS release PDCCH on one of subframes i−k_(m) (k_(m)∈K,0≦m≦M−1) from a serving cell c, n_(HARQ,c)=(the number of transportblocks received on the subframes i−k_(m))+1. If a UE does not receive anSPS release PDCCH on one of subframes i−k_(m) (k_(m)∈K: {k₀,k₁, . . .k_(M−1)}, 0≦m≦M−1) from a serving cell c, n_(HARQ,c)=(the number oftransport blocks received on the subframes i−k_(m)). In case of FDD,n_(HARQ) is given similarly to the case of TDD and M=1 and k₀=4.

More specifically, in case of TDD,

$n_{HARQ} = {\sum\limits_{c = 0}^{C - 1}\; {\sum\limits_{k_{m} \in K}N_{k_{m},c}^{received}}}$

may be given. C denotes the number of configured serving cells. N_(k)_(m) _(c) ^(received) denotes the number of transport blocks and SPSrelease PDCCHs received on the subframes i−k_(m) of the serving cell c.In case of FDD,

$n_{HARQ} = {\sum\limits_{c = 0}^{C - 1}\; N_{c}^{received}}$

may be given. N_(c) ^(received) denotes the number of transport blocksand SPS release PDCCHs received on subframes i−4 of the serving cell c.

g(i) denotes a current PUCCH power control adjustment state. Morespecifically,

${g(i)} = {{g\left( {i - 1} \right)} + {\sum\limits_{m = 0}^{M - 1}\; {\delta_{PUCCH}\left( {i - k_{m}} \right)}}}$

may be given. g(0) is a first value after reset. δ_(PUCCH) is aUE-specific correction value and is also called a TPC command. δ_(PUCCH)is included in a PDCCH having a DCI format 1A/1B/1D/1/2A/2/213/2C incase of PCell. In addition, δ_(PUCCH) is joint-coded with anotherUE-specific PUCCH correction value on a PDCCH having a DCI format 3/3A.

Embodiment: PUCCH Power Control in the Case Where Simultaneous PUCCH andPUSCH Transmission Mode is Configured

FIG. 30 shows a UL transmission process according to the existing 3GPPRel-8/9. FIG. 30 shows a buffer status reporting (BSR) and SR process ofa MAC layer.

Referring to FIG. 30, if UL data becomes available for transmission in ahigher layer entity (e.g., an RLC entity or a PDCP entity) (S3002), aBSR process is triggered (S3004). The BSR process is used to provideinformation about the amount of available data for transmission in a ULbuffer of a UE to a serving eNB. If the BSR process is triggered, theMAC layer determines whether UL resources (e.g., UL-SCH resources)allocated for new transmission are present (S3006). If the allocatedUL-SCH resources are present, the MAC layer generates a MAC PDU (S3008).The MAC PDU may include pending data available for transmission and/orBSR MAC control element (CE). Thereafter, the MAC layer transmits thegenerated MAC PDU to a physical (PHY) layer (S3010). The MAC PDU istransmitted to the PHY layer via a UL-SCH channel. In view of the PHYlayer, the MAC PDU is a UL-SCH transmission block. Thereafter, thetriggered BSR process is cancelled (S3012). If pending data is presentin the buffer after the BSR MAC CE is transmitted, the eNB may allocateUL-SCH resources to the UE in consideration of the BSR and the UE maytransmit pending data using the allocated resources.

In contrast, if the UL resources allocated for new transmission are notpresent, the SR process is triggered (S3014). The SR process is used torequest UL-SCH resources for new transmission. If the SR process istriggered, the MAC layer instructs the PHY layer to signal an SR(S3016). The PHY layer transmits the SR on an SR subframe (a subframeconfigured for SR transmission) according to the instruction of the MAClayer. Thereafter, the MAC layer determines whether UL-SCH resourcesavailable for new data transmission or BSR are present or not (S3018).If the available UL-SCH resources are not present, the SR process ispending and steps S3014 to S3016 are repeated. In contrast, if theavailable UL-SCH resources are present, that is, if UL-SCH resources areallocated through UL grant, the triggered SR process is cancelled(S3020). If the UL-SCH resources become available by the SR process,steps S3006 to S3012 are performed according to the BSR process.

In summary, in the existing 3GPP Rel-8/9, the SR is triggered and noPUSCH is transmitted on the SR subframe (that is, UL-SCHresources/UL-SCH transport blocks for the SR subframe are not present),the UE transmits a positive SR through a PUCCH format 1. In contrast, ifthe SR is triggered and a PUSCH is transmitted on the SR subframe (thatis, UL-SCH resources/UL-SCH transport blocks for the SR subframe arepresent), the UE drops SR transmission and transmits a BSR MAC CE and/orpending data through the PUSCH.

Meanwhile, in the existing 3GPP Rel-8/9, the SR may be triggered and anaperiodic CQI only PUSCH may be triggered in the SR subframe. The CQIonly PUSCH signal includes only a CQI and does not include data (thatis, a UL-SCH transport block). Accordingly, if the CQI only PUSCH istriggered, since available UL-SCH resources for new transmission are notpresent, the triggered SR is not cancelled. That is, simultaneoustransmission of the CQI only PUSCH signal and the SR PUCCH signal isrequired on the same subframe. However, in the existing 3GPP Rel-8/9,simultaneous transmission of the PUCCH and PUSCH is not allowed.Accordingly, in this example, the UE regards CQI only PUSCH triggeringas mis-configuration. As a result, the UE drops aperiodic CQI PUSCHtransmission and transmits only the positive SR through the PUCCHformat 1. For reference, if the value of a CQI request field is 1, a MCSindex I_(MCS) is 29 and the number of allocated PRBs is less than orequal to 4 (N_(PRB)≦4) in a PDCCH signal for UL grant, the UE analyzesthe signaling as CQI only PUSCH allocation.

As described above, in the existing 3GPP Rel-8/9, simultaneoustransmission of the PUCCH and PUSCH is inhibited for UL transmissionhaving a low peak-to-average power ratio (PAPR) property. However, inthe 3GPP Rel-10, a simultaneous PUCCH-and-PUSCH transmission mode may beconfigured through RRC signaling. That is, the UE may transmit a UCI(e.g., HARQ-ACK and/or SR) through the PUCCH and transmit only a CSI(e.g., CQI) or data (e.g., UL-SCH transport block) through the PUSCH onthe same subframe.

According to the conventional power control method of the PUCCH format 3described with reference to Equation 17, if control information istransmitted on an SR subframe through a PUCCH format 3, the controlinformation always includes an SR bit (e.g., 1 bit) and an added SR bitis used to increase transmit power of the PUCCH (n_(SR)=1). In theconventional power control method, it is also assumed that simultaneoustransmission of the PUCCH and PUSCH is not configured. That is, only thePUCCH or PUSCH may be transmitted on one subframe, and controlinformation which is scheduled to be transmitted through the PUCCH istransmitted through the PUSCH if the PUCCH and the PUSCH should betransmitted on the same subframe. Accordingly, transmission of the PUCCHon the SR subframe indicates that UL-SCH resources/UL-SCH transportblocks for the SR subframe are not present. In this case, the SR bitadded to the control information may be always used to carry validinformation.

However, in consideration of configuring the UE with the simultaneousPUCCH-and-PUSCH transmission mode, it is necessary to more efficientlyperform power control. For example, if it is assumed that the UE isconfigured in the simultaneous PUCCH-and-PUSCH transmission mode, ascenario in which the PUCCH format 3 signal and the PUSCH signal aresimultaneously transmitted on the SR subframe is possible. In this case,the PUCCH format 3 signal may include an SR bit and the PUSCH signal mayinclude a UL-SCH transport block. In addition, the PUSCH signal mayinclude only a CSI. As described with reference to FIG. 30, if theUL-SCH resources/UL-SCH transport blocks are present for the SRsubframe, the triggered SR is cancelled. That is, presence of the UL-SCHtransport block in the PUSCH signal may indicate a negative SR.Accordingly, if the PUSCH signal includes the UL-SCH transport block,the SR bit included in the PUSCH format 3 signal carries redundantinformation. In this case, since the SR bit may have any value (don'tcare), the value of the SR bit may be regarded as invalid information.That is, if the UL-SCH transport block is present for the SR subframe,the SR bit included in the PUCCH format 3 signal corresponds to a dummybit without information. Accordingly, if the case where the dummy bit isincluded in the PUCCH format 3 signal and the case where the dummy bitis not included in the PUCCH format 3 signal are equally treated duringPUCCH power control, power efficiency may be decreased.

Hereinafter, the method for efficiently performing PUCCH power controlin consideration of the simultaneous PUCCH-and-PUSCH transmission modewill be described. The following description will focus upon the methodof correcting h(.) according to the UL signal transmission scenario ofEquation 17.

If the simultaneous transmission of the PUCCH and PUSCH is configured,the UL transmission scenario is as follows:

(1) If the PUCCH format 3 signal for HARQ-ACK and the PUSCH signal aresimultaneously transmitted on a non-SR subframe, the PUSCH signal mayinclude data (e.g., UL-SCH transport block) or only a CSI.

(2) If the PUCCH format 3 signal for HARQ-ACK and the PUSCH signal aresimultaneously transmitted on the SR subframe, the PUSCH signal mayinclude data (e.g., UL-SCH transport block) or only a CSI.

In case of (1), the SR bit is not included in the control informationfor the PUCCH format 3. Accordingly, h(.) for power control of the PUCCHmay be determined by using the following equation.

$\begin{matrix}{{h( \cdot )} = {\frac{n_{HARQ} + n_{SR} - 1}{2} = \frac{n_{HARQ} + 0 - 1}{2}}} & {{Equation}\mspace{14mu} 18}\end{matrix}$

In case of (2), the following case will be considered in considerationof the SR.

i) The HARQ-ACK and SR may be transmitted through the PUCCH format 3 andonly the CSI may be transmitted through the PUSCH. In this case, sincethe SR bit is a valid value indicating actual SR information, it ispossible to perform power control of the PUCCH in consideration of theSR bit. In this case, h(.) for power control of the PUCCH may bedetermined by using the following equation.

$\begin{matrix}{{h( \cdot )} = {\frac{n_{HARQ} + n_{SR} - 1}{2} = \frac{n_{HARQ} + 1 - 1}{2}}} & {{Equation}\mspace{14mu} 19}\end{matrix}$

ii) The HARQ-ACK and SR may be transmitted through the PUCCH format 3and the UL-SCH transport block (e.g., BSR or data) may be transmittedthrough the PUSCH. In this example, the SR bit may be used to indicateactual SR information, regardless of whether the UL-SCH transport blockis transmitted on the SR subframe. In this example, if the UL-SCHtransport block is transmitted on the SR subframe, the SR bit indicatesa value (e.g., 0) always indicating a negative SR. Accordingly, if theUL-SCH transport block is present on the SR subframe, the SR bit in thePUCCH signal may be used to check error of the control informationtransmitted through the PUCCH. Since the SR bit carries validinformation, h(.) for power control of the PUCCH may be determined byusing the following equation.

$\begin{matrix}{{h( \cdot )} = {\frac{n_{HARQ} + n_{SR} - 1}{2} = \frac{n_{HARQ} + 1 - 1}{2}}} & {{Equation}\mspace{14mu} 20}\end{matrix}$

iii) The HARQ-ACK and SR may be transmitted through the PUCCH format 3and the UL-SCH transport block (e.g., BSR or data) may be transmittedthrough the PUSCH. In this example, the SR bit may be treated as a dummybit without information. That is, if the UL-SCH transport block is notpresent on the SR subframe, the SR bit included in the PUCCH indicatesan actual SR bit (that is, actual SR information or valid bit). In thiscase, the MAC layer of the UE signals SR indication information to thePHY layer and the PHY layer sets the value of the SR bit according tothe SR indication information. The case where the UL-SCH transport blockis not present on the SR subframe also includes the case where the CSIonly PUSCH is transmitted on the SR subframe (that is, an aperiodic CSIwithout a UL-SCH transport block). In contrast, if the UL-SCH transportblock is present on the SR subframe, the SR bit included in the PUCCHsignal indicates a dummy bit (that is, dummy information or invalidbit). In this case, the MAC layer may not signal the SR indicationinformation to the PHY layer. Instead, the PHY layer may set the SR bitto a dummy value, depending on whether or not a condition is satisfied.The dummy bit may have a predetermined value. For example, the dummy bitmay be set to a predetermined value of 0 or 1 and may be preferably setto 0.

More specifically, control information generated by multiplexing aHARQ-ACK bit stream [b₀ b₁ . . . b_(m−1)] and an SR bit s₀ may betransmitted through the PUCCH format 3 and a UL-SCH transport block(e.g., BSR or data) may be transmitted through the PUSCH. Multiplexingof the HARQ-ACK bit stream and the SR bit includes attaching the SR bits₀ to the end (or the front) of the HARQ-ACK bit stream [b₀ b₁ . . .b_(m−1)] so as to generate [b₀ b₁ . . . b_(m−1) s₀] and performingcoding (that is, joint coding). In this example, the SR bit functions asa bit fixedly inserted for avoiding ambiguity of the control informationsize. The SR bit is set to a predetermined value (e.g., 0 or 1 andpreferably 0) and the eNB may ignore the SR bit when decoding thecontrol information. Instead, the eNB may determine whether or not theSR of the UE is triggered according to presence/absence of the UL-SCHtransport block (e.g., BSR or data) of the PUSCH signal.

As described above, in this example, since the SR bit does not indicateactual SR information, the SR bit may not be considered during powercontrol. In other words, if the PUCCH and the PUSCH are simultaneouslytransmitted on the SR subframe, the HARQ-ACK and the dummy SR may betransmitted through the PUCCH format 3 and the UL-SCH transport block(e.g., BSR or data) may be transmitted through the PUSCH. h(.) for powercontrol of the PUCCH may be determined by the following equation.

$\begin{matrix}{{h( \cdot )} = {\frac{n_{HARQ} + n_{SR} - 1}{2} = \frac{n_{HARQ} + 0 - 1}{2}}} & {{Equation}\mspace{14mu} 21}\end{matrix}$

In this example, unlike Equation 17, since power control of the PUCCH isperformed by n_(SR)=0, not by n_(SR)=1, even in the SR subframe, powerefficiency for UL transmission can be increased. In this example, n_(SR)may indicate the number of valid SR bits (SR bits having actualinformation). In addition, if the HARQ-ACK is transmitted on the SRsubframe through the PUCCH format 3, the decoding efficiency of the eNBmay be increased by always equally maintaining the payload size of thecontrol information using the dummy SR bit.

iv) The HARQ-ACK may be transmitted through the PUCCH format 3 and theUL-SCH transport block (e.g., BSR or data) may be transmitted throughthe PUSCH. In this example, the SR bit is dropped. That is, if thepayload size of the control information included in the PUCCH signal isN when the UL-SCH transport block is not present on the SR subframe, thepayload size of the control information included in the PUCCH signalbecomes N−1 when the UL-SCH transport block is present on the SRsubframe.

Since the SR bit is not transmitted, although the PUCCH is transmittedon the SR subframe, unlike Equation 17, power control of the PUCCH isperformed by n_(SR)=0, not by n_(SR)=1. Accordingly, h(.) for powercontrol of the PUCCH may be determined by the following equation.

$\begin{matrix}{{h( \cdot )} = {\frac{n_{HARQ} + n_{SR} - 1}{2} = \frac{n_{HARQ} + 0 - 1}{2}}} & {{Equation}\mspace{14mu} 22}\end{matrix}$

The above-described method may be generalized as follows regardless ofthe configuration of the simultaneous PUCCH-and-PUSCH transmission mode.

$\begin{matrix}{{h( \cdot )} = \frac{n_{HARQ} + n_{SR} - 1}{2}} & {{Equation}\mspace{14mu} 23}\end{matrix}$

If the PUCCH format 3 signal is transmitted on a non-SR subframe,n_(SR)=0.

If the PUCCH format 3 signal is transmitted on an SR subframe,

-   -   if the UL-SCH transport block is not present, n_(SR)=1, and    -   if the UL-SCH transport block is present, n_(SR)=1 (Equation 20)        and n_(SR)=0 (Equations 21 to 22).

FIG. 31 shows a process of transmitting control information via a PUCCHaccording to an embodiment of the present invention.

Referring to FIG. 31, an eNB transmits a PDCCH and a PDSCH correspondingthereto to a UE (S3102). At least one of the PDCCH and the PDSCH may bereceived on one SCell. Thereafter, the UE generates control informationfor transmission through the PUCCH format 3. The control informationincludes HARQ-ACK information for the PDSCH. If the HARQ-ACK istransmitted on the SR subframe, the control information further includesan SR bit. The SR bit is attached to the end (or the front) of theHARQ-ACK bit stream and the SR bit and the HARQ-ACK bit stream arejoint-coded. The PUCCH format 3 signal is generated from the controlinformation through the process shown in FIG. 29. The UE sets PUCCHtransmit power for PUCCH transmission (S3104) and transmits the PUCCHformat 3 signal to the eNB through a power control process, etc.(S3106).

In this example, if the PUCCH format 3 signal is transmitted on the SRsubframe, transmit power for PUCCH transmission is set in considerationof whether or not the UL-SCH transport block associated with the SRsubframe is present. For example, the transmit power setting method ofEquation 17 is used and h(.) may be replaced with Equation 23 inconsideration of whether or not the UL-SCH transport block associatedwith the SR subframe is present. The SR subframe indicates the subframeconfigured for SR transmission. The SR subframe is configured by ahigher layer (e.g., RRC) and may be specified by a period/offset.

FIG. 32 is a diagram showing a BS and a UE applicable to the presentinvention.

Referring to FIG. 32, a wireless communication system includes a BS 110and a UE 120. The BS 110 includes a processor 112, a memory 114 and aradio frequency (RF) unit 116. The processor 112 may be configured toimplement the procedures and/or methods proposed by the presentinvention. The memory 114 is connected to the processor 112 so as tostore a variety of information associated with the operation of theprocessor 112. The RF unit 116 is connected to the processor 112 so asto transmit and/or receive a RF signal. The UE 120 includes a processor122, a memory 124 and a RF unit 126. The processor 122 may be configuredto implement the procedures and/or methods proposed by the presentinvention. The memory 124 is connected to the processor 122 so as tostore a variety of information associated with the operation of theprocessor 122. The RF unit 126 is connected to the processor 122 so asto transmit and/or receive a RF signal. The BS 110 and/or the UE 120 mayhave a single antenna or multiple antennas.

The aforementioned embodiments are achieved by combination of structuralelements and features of the present invention in a predetermined type.Each of the structural elements or features should be consideredselectively unless specified separately. Each of the structural elementsor features may be carried out without being combined with otherstructural elements or features. Also, some structural elements and/orfeatures may be combined with one another to constitute the embodimentsof the present invention. The order of operations described in theembodiments of the present invention may be changed. Some structuralelements or features of one embodiment may be included in anotherembodiment, or may be replaced with corresponding structural elements orfeatures of another embodiment. Moreover, it will be apparent that someclaims referring to specific claims may be combined with another claimsreferring to the other claims other than the specific claims toconstitute the embodiment or add new claims by means of amendment afterthe application is filed.

The embodiments of the present invention have been described based onthe data transmission and reception between the base station and theuser equipment. A specific operation which has been described as beingperformed by the base station may be performed by an upper node of thebase station as the case may be. In other words, it will be apparentthat various operations performed for communication with the userequipment in the network which includes a plurality of network nodesalong with the base station can be performed by the base station ornetwork nodes other than the base station. The base station may bereplaced with terms such as a fixed station, Node B, eNode B (eNB), andaccess point. Also, the user equipment may be replaced with terms suchas mobile station (MS) and mobile subscriber station (MSS).

The embodiments according to the present invention can be implemented byvarious means, for example, hardware, firmware, software, or theircombination. If the embodiment according to the present invention isimplemented by hardware, the embodiment of the present invention can beimplemented by one or more application specific integrated circuits(ASICs), digital signal processors (DSPs), digital signal processingdevices (DSPDs), programmable logic devices (PLDs), field programmablegate arrays (FPGAs), processors, controllers, microcontrollers,microprocessors, etc.

If the embodiment according to the present invention is implemented byfirmware or software, the embodiment of the present invention may beimplemented by a type of a module, a procedure, or a function, whichperforms functions or operations described as above. A software code maybe stored in a memory unit and then may be driven by a processor. Thememory unit may be located inside or outside the processor to transmitand receive data to and from the processor through various means whichare well known.

It will be apparent to those skilled in the art that variousmodifications and variations can be made in the present inventionwithout departing from the spirit or scope of the inventions. Thus, itis intended that the present invention covers the modifications andvariations of this invention provided they come within the scope of theappended claims and their equivalents.

INDUSTRIAL APPLICABILITY

The present invention is applicable to a terminal, a BS or anotherdevice of a wireless mobile communication system. More specifically, thepresent invention is applicable to a method and apparatus fortransmitting uplink control information.

What is claimed is:
 1. A method for transmitting control information bya communication apparatus in a wireless communication system, the methodcomprising: determining a transmit power of a physical uplink controlchannel (PUCCH) signal by using n_(HARQ)+n_(SR), when the PUCCH signalincludes hybrid automatic repeat request acknowledgement (HARQ-ACK) andscheduling request (SR) bits; and transmitting the PUCCH signal usingthe determined transmit power at a subframe, wherein n_(HARQ) is a valueassociated with HARQ-ACK, and n_(SR) is a value associated with SR anddetermined as follows: n_(SR) is 0, if a physical uplink shared channel(PUSCH) signal including a data block for an uplink shared channel(UL-SCH) data is allocated at the subframe, and n_(SR) is 1, if thePUSCH signal including the data block for the UL-SCH is not allocated atthe subframe.
 2. The method of claim 1, wherein the data block for theUL-SCH includes a buffer status report (BSR).
 3. The method of claim 1,wherein the transmit power for the PUCCH signal is determined by usingthe following equation:${h( \cdot )} = \frac{n_{HARQ} + n_{SR} - 1}{2}$ where n_(HARQ)includes a number of the HARQ-ACK bit(s) or a number of receivedtransport block(s), and N is an integer larger than
 1. 4. The method ofclaim 3, wherein N is
 2. 5. The method of claim 4, wherein n_(HARQ)further includes a number of semi-persistent scheduling (SPS) releasephysical downlink control channel(s) (PDCCH(s)) received over the two ormore configured cells.
 6. The method of claim 4, wherein the transmitpower for the PUCCH signal is determined by using the followingequation: ${P_{PUCCH}(i)} = {\min \begin{Bmatrix}{{{P_{{CMAX},c}(i)},}\mspace{506mu}} \\{P_{0_{—}{PUCCH}} + {PL}_{c} + {h( \cdot )} + {\Delta_{F_{—}{PUCCH}}(F)} + {\Delta_{TxD}\left( F^{\prime} \right)} + {g(i)}}\end{Bmatrix}}$ where P_(PUCCH)(i) denotes the transmit power for thePUCCH signal, P_(CMAX,c)(i) denotes a maximum transmit power configuredfor a serving cell c, P₀ _(_) _(PUCCH) denotes a parameter configured bya higher layer, PL_(c) denotes a downlink path loss estimation value ofthe serving cell c, Δ_(F PUCCH)(F) denotes a value corresponding to aPUCCH format, Δ_(T×D)(F′) denotes a value configured by the higher layeror 0, and g(i) denotes a current PUCCH power control adjustment state,and i denotes a subframe index where the PUCCH signal is transmitted. 7.The method of claim 1, wherein the SR bit 1-bit and is attached to anend of the HARQ-ACK bit(s).
 8. The method of claim 7, wherein the SR bitis set to 1 in case of a positive SR, and the SR bit is set to 0 in caseof a negative SR.
 9. The method of claim 1, wherein the HARQ-ACK and SRbits are joint-coded.
 10. A communication apparatus for use in awireless communication system, the communication apparatus comprising: aprocessor that determines a transmit power of a physical uplink controlchannel (PUCCH) signal by using n_(HARQ)+n_(SR), when the PUCCH signalincludes hybrid automatic repeat request acknowledgement (HARQ-ACK) andscheduling request (SR) bits; and a radio frequency (RF) unit thattransmits the PUCCH signal using the determined transmit power at asubframe, wherein n_(HARQ) is a value associated with HARQ-ACK, andn_(SR) is a value associated with SR and determined as follows: n_(SR)is 0, if a physical uplink shared channel (PUSCH) signal including adata block for an uplink shared channel (UL-SCH) data is allocated atthe subframe, and n_(SR) is 1, if the PUSCH signal including the datablock for the UL-SCH is not allocated at the subframe.
 11. Thecommunication apparatus of claim 10, wherein the data block for theUL-SCH includes a buffer status report (BSR).
 12. The communicationapparatus of claim 10, wherein the transmit power for the PUCCH signalis determined by using the following equation:${h( \cdot )} = \frac{n_{HARQ} + n_{SR} - 1}{2}$ where n_(HARQ)includes a number of the HARQ-ACK bit(s) or a number of receivedtransport block(s), and N is an integer larger than
 1. 13. Thecommunication apparatus of claim 12, wherein N is
 2. 14. Thecommunication apparatus of claim 13, wherein n_(HARQ) further includes anumber of semi-persistent scheduling (SPS) release physical downlinkcontrol channel(s) (PDCCH(s)) received over the two or more configuredcells.
 15. The communication apparatus of claim 13, wherein the transmitpower for the PUCCH signal is determined by using the followingequation: ${P_{PUCCH}(i)} = {\min \begin{Bmatrix}{{{P_{{CMAX},c}(i)},}\mspace{506mu}} \\{P_{0_{—}{PUCCH}} + {PL}_{c} + {h( \cdot )} + {\Delta_{F_{—}{PUCCH}}(F)} + {\Delta_{TxD}\left( F^{\prime} \right)} + {g(i)}}\end{Bmatrix}}$ where P_(PUCCH) (i) denotes the transmit power for thePUCCH signal, P_(CMAX,c)(i) denotes a maximum transmit power configuredfor a serving cell c, P₀ _(_) _(PUCCH) denotes a parameter configured bya higher layer, PL_(c) denotes a downlink path loss estimation value ofthe serving cell c, Δ_(F) _(_) _(PUCCH)(F) denotes a value correspondingto a PUCCH format, Δ_(T×D)(F′) denotes a value configured by the higherlayer or 0, and g(i) denotes a current PUCCH power control adjustmentstate, and i denotes a subframe index where the PUCCH signal istransmitted.
 16. The communication apparatus of claim 10, wherein the SRbit 1-bit and is attached to an end of the HARQ-ACK bit(s).
 17. Thecommunication apparatus of claim 16, wherein the SR bit is set to 1 incase of a positive SR, and the SR bit is set to 0 in case of a negativeSR.
 18. The communication apparatus of claim 10, wherein the HARQ-ACKand SR bits are joint-coded.